data sheet aat278952ebad10ee97eea25d5e-d7d40819259e7d3022d9ad53e3694148.r84.cf3.rackcdn…skyworks...

1

AAT2789Low Noise, High Frequency Dual Step-Down Converter

DATA SHEET

Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • [email protected] • www.skyworksinc.com 202047A • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • June 11, 2012

General DescriptionThe AAT2789 is a 2-channel synchronous step-down converter operating from an input voltage range of 2.7V to 5.5V, making it the ideal choice for single-cell Lithium-ion/polymer battery powered systems or low voltage 3.3V and 5V based consumer equipment.

Channel 1 delivers up to 1700mA output current while Channel 2 delivers up to 800mA. Both converters incor-porate a unique low noise architecture which reduces output ripple and spectral noise.

The AAT2789 uses a high switching frequency to mini-mize external filter sizing. Peak current mode control eliminates external compensation while optimizing tran-sient performance and stability.

The AAT2789 requires a minimum of external compo-nents to realize a high efficiency dual-output step-down converter while minimizing solution size and footprint.

Each of the step-down regulators has an independent input and enable pin. Externally adjustable output volt-age is provided. Light load operating mode provides high efficiency over the entire load range. Low quiescent cur-rent enables excellent life for battery powered systems.

The AAT2789 is available in a 3x4mm Pb-free 16-pin TDFN package and is rated over the -40°C to 85°C oper-ating temperature range.

Features• VIN Range: 2.7V to 5.5V• Output Voltage Range: 0.6V to VIN

• Low Noise Light Load Mode• Low Ripple PWM Mode• Output Current:▪ Channel 1: 1700mA▪ Channel 2: 800mA

• Highly Efficient Step-Down Converters• Low RDS(ON) Integrated Power Switches• 100% Duty Cycle• High Switching Frequency• Peak Current Mode Control• Internal Compensation• Excellent Transient Response• Internal Soft Start• Fast Turn-On Time• Over-Temperature Protection• Current Limit Protection• Low Profile TDFN34-16 Package• -40°C to 85°C Temperature Range

Applications• Cellular and Smart Phones• Digital Cameras• Handheld Instruments• Mass Storage Systems• Microprocessor / DSP Core / IO Power• PDAs and Handheld Computers• Portable Media Players• USB Devices• Wireless Data Systems

Typical Application

L11.5μH

L23.3μH

R159.0kR259.0k

R459.0k

R3267k

VOUT1

1.2V, 1700mA

VOUT2

3.3V, 800mALX2

PGND2FB2

AGND2

AGND1

LX1

PGND1FB1

C110μF6.3V

C310μF6.3V

C222μF6.3V

VIN: 2.7V - 5.5V

VP1,2

EN1EN2

AAT2789TDFN34-16

VCC1,2

2


DATA SHEET


Pin DescriptionsPin # Symbol Function

1 N/C No connect.

2 PGND2 Power ground pin for Channel 2 step-down converter. Connect return of Channel 2 input and output capacitors close to this pin for best noise performance.

3 LX2 Channel 2 step-down converter switching pin. Connect output inductor to this pin. Inductor value is determined by output voltage.

4 VP2 Input supply voltage pin for Channel 2 step-down converter. Connect a 10μF ceramic input capacitor close to this pin or connect to VP1. Operating input voltage range is 2.7V to 5.5V.

5 VCC1 Input supply pin for Channel 1. Must be closely decoupled.6 EN1 Enable Channel 1 input pin. Active high.

7,8 VP1 Input supply voltage pin for Channel 1 step-down converter. Connect a 10μF ceramic input capacitor close to this pin. Operating input voltage range is 2.7V to 5.5V.

9 LX1 Channel 1 step-down converter switching pin. Connect output inductor to this pin. Inductor value is determined by output voltage.

10 PGND1 Power ground pin for Channel 1 step-down converter. Connect return of Channel 1 input and output capacitors close to this pin for best noise performance.

11 FB1 Feedback pin for Channel 1. Connect an external resistor divider to this pin to program the output volt-age to the desired value.

12 AGND1 Signal ground for Channel 1.13 VCC2 Input supply pin for Channel 2. Must be closely decoupled.14 EN2 Enable Channel 2 input pin. Active high.

15 FB2 Feedback pin for Channel 2. Connect an external resistor divider to this pin to program the output volt-age to the desired value.

16 AGND2 Signal Ground for Channel 2.

EP EP Exposed paddle. Connect to PGND1 and PGND2 as close as possible to the device. Use properly sized vias for thermal coupling to the ground plane. See PCB layout guidelines.

Pin Configuration

TDFN34-16(Top View)

LX2

VP2

VCC1

N/C

PGND23

EN1

VP1

VP1

EN2

VCC2

AGND1

AGND2

FB2

FB1

PGND1

LX1

4

5

1

2

6

7

8

14

13

12

16

15

11

10

9

3


DATA SHEET


Absolute Maximum Ratings1

Symbol Description Value UnitsVIN VP1, VP2, VCC1, VCC2 voltages to PGND, AGND 6.0 VVLX VLX1, VLX2 to PGND, AGND -0.3 to VIN + 0.3 VVFB VFB1, VFB2 to PGND, AGND -0.3 to VIN + 0.3 VVEN VEN1, VEN2 to PGND, AGND -0.3 to 6.0 VTJ Operating Junction Temperature Range -40 to 150 C

TLEAD Maximum Soldering Temperature (at leads, 10 sec) 300 C

Thermal InformationSymbol Description Value Units

PD Maximum Power Dissipation2 2.0 WJA Thermal Resistance3 50 C/W

1. Stresses above those listed in Absolute Maximum Ratings may cause permanent damage to the device. Functional operation at conditions other than the operating conditions specified is not implied. Only one Absolute Maximum Rating should be applied at any one time.

2. Mounted on a FR4 board.3. Derate 20mW/°C above 25°C ambient temperature.

4


DATA SHEET


Electrical Characteristics1

VIN = 3.6V, TA = -40°C to 85°C, unless noted otherwise. Typical values are at TA = 25°C.

Symbol Description Conditions Min Typ Max UnitsChannel 1: 1700mA Step-Down Converter

VP1, VCC1 Input Voltage 2.7 5.5 V

VUVLO1 UVLO ThresholdVP1 Rising 2.4 VVP1 Hysteresis 250 mVVP1 Falling 1.7 V

VOUT1 Output Voltage Range 0.6 VP1 VVOUT1(TOL) Output Voltage Tolerance IOUT1 = 0A to 1.7A; VP1 = 2.7V to 5.5V -3.0 3.0 %

IQ1 Quiescent Current No load, VEN1 = VP1, VEN2 = AGND 42 90 μAISHDN1 Shutdown Current VEN1 = GND 1.0 μAILIM1 Current Limit 1800 mA

RDSON(H)1 High Side On-Resistance 120 mΩRDSON(L)1 Low Side On-Resistance 85 mΩΔVLOADREG1 Load Regulation IOUT1 = 0A to 1.7A 0.5 %ΔVLINEREG1 / ΔVP1

Line Regulation VP1 = 2.7V to 5.5V 0.2 %/V

FOSC1 Oscillator Frequency 1.12 1.40 1.68 MHzTS1 Start-Up Time From Enable-1 to Output-1 Regulation 150 μs

Channel 2: 800mA Step-Down ConverterVP2, VCC2 Input Voltage 2.7 5.5 V

VUVLO2 UVLO ThresholdVP2 Rising 2.7 VVP2 Hysteresis 100 mVVP2 Falling 1.7 V

VOUT2 Output Voltage Range 0.6 VP2 VVOUT2(TOL) Output Voltage Tolerance IOUT2 = 0A to 800mA, VP2 = 2.7V to 5.5V -3.0 3.0 %

IQ2 Quiescent Current No load, VEN2 = VP2, VEN1 = AGND 37 70 μAISHDN2 Shutdown Current VEN2 = GND 1.0 μAILIM2 Current Limit 900 mA

RDSON(H)2 High Side On-Resistance 330 mΩRDSON(L)2 Low Side On-Resistance 275 mΩΔVLOADREG2 Load Regulation IOUT2= 0mA to 800mA 0.5 %ΔVLINEREG2 / ΔVP2

Line Regulation VP2 = 2.7V to 5.5V 0.1 %/V

FOSC2 Oscillator Frequency 0.9 2.0 2.6 MHzTS2 Start-Up Time From Enable-2 to Output-2 Regulation 150 μs

Over-Temperature, EN Logic

TSD1,2Over-Temperature Shutdown Threshold 140 °COver-Temperature Shutdown Hysteresis 15 °C

VEN1,2(L) Enable Threshold Low 0.6 VVEN1,2(H) Enable Threshold High 1.4 VIEN(1,2 Input Low Current -1.0 1.0 μA

1. The AAT2789 is guaranteed to meet performance specifications over the –40°C to +85°C operating temperature range, and is assured by design, characterization and correla-tion with statistical process controls.

5


DATA SHEET


Typical Characteristics – Channel 1

Efficiency vs. Output Current(VOUT = 3.3V)

Output Current (mA)

Eff

icie

ncy (

%)

30

40

50

60

70

80

90

100

0.1 1 10 100 1000 10000

VIN = 3.6V

VIN = 4.2V

VIN = 5V

Load Regulation vs. Output Current(VOUT = 3.3V)

Output Current (mA)

Lo

ad

Reg

ula

tio

n (

%)

-1.0

-0.5

0.0

0.5

1.0

0.1 1 10 100 1000 10000

VIN = 3.6V

VIN = 4.2V

VIN = 5V


Output Current (mA)

Eff

icie

ncy (

%)

30

40

50

60

70

80

90

100

0.1 1 10 100 1000 10000

VIN = 2.7V

VIN = 3.6V

VIN = 4.2V


Output Current (mA)

Lo

ad

Reg

ula

tio

n (

%)

-1.0

-0.5

0.0

0.5

1.0

0.1 1 10 100 1000 10000

VIN = 2.7V

VIN = 3.6V

VIN = 4.2V


Output Current (mA)

Eff

icie

ncy (

%)

30

40

50

60

70

80

90

100

0.1 1 10 100 1000 10000

VIN = 2.7V

VIN = 3.6V

VIN = 4.2V


Output Current (mA)

Lo

ad

Reg

ula

tio

n (

%)

-1.0

-0.5

0.0

0.5

1.0

0.1 1 10 100 1000 10000

VIN = 2.7V

VIN = 3.6V

VIN = 4.2V

6


DATA SHEET



Quiescent Current vs. Input Voltage (VOUT = 1.8V; No Load)

Input Voltage (V)

Qui

esce

nt C

urre

nt (µ

A)

20

30

40

50

60

70

80

2.7 2.9 3.1 3.3 3.5 3.7 3.9 4.1 4.3 4.5 4.7 4.9 5.1 5.3 5.5

10

0

85°C

25°C

-40°C

Output Voltage Error vs. Temperature(VOUT = 1.8V; IOUT = 1A)

Temperature (°C)

Ou

tpu

t V

olt

ag

e E

rro

r (%

)

-3.5

-3.0

-2.5

-2.0

-1.5

-1.0

-0.5

0.0

0.5

1.0

1.5

-40 -30 -20 -10 0 10 20 30 40 50 60 70 80 90

Output Voltage vs. Input Voltage(VOUT = 1.8V; IOUT = 1A)

Input Voltage (V)

Ou

tpu

t V

olt

ag

e (

V)

1.73

1.74

1.75

1.76

1.77

1.78

1.79

1.80

1.81

1.82

2.7 2.9 3.1 3.3 3.5 3.7 3.9 4.1 4.3 4.5 4.7 4.9 5.1 5.3 5.5

85°C

25°C

-40°C

Switching Frequency vs. Temperature(VOUT = 1.8V; IOUT = 1A)

Temperature (°C)

Sw

itch

ing

Fre

qu

en

cy (

MH

z)

1.42

1.44

1.46

1.48

1.5

1.52

1.54

1.56

-40 -30 -20 -10 0 10 20 30 40 50 60 70 80 90

Load Transient Response(VOUT = 1.8V)

Time (100µs/div)

Ou

tpu

t V

olt

ag

e (

AC

co

up

led

)

(to

p)(

mV

)

Ou

tpu

t Cu

rren

t

(bo

ttom

) (A)

-0.60

-0.50

-0.40

-0.30

-0.20

-0.10

0.00

0.10

0.20

0.8

1.0

1.2

1.4

1.6

1.8

2.0

2.2

2.4

Load Transient Response(VOUT = 1.8V; CFF = 100pF)

Time (100µs/div)

Ou

tpu

t V

olt

ag

e (

AC

co

up

led

)

(to

p)(

mV

)

Ou

tpu

t Cu

rren

t

(bo

ttom

) (A)

-0.60

-0.50

-0.40

-0.30

-0.20

-0.10

0.00

0.10

0.20

0.8

1.0

1.2

1.4

1.6

1.8

2.0

2.2

2.4

7


DATA SHEET



Line Transient Response (VOUT = 1.8V; IOUT = 1.5A; CFF = 100pF)

Time (100µs/div)

Inpu

t Vol

tage

(top)

(V)

Output Voltage (A

C coupled)

(bottom) (V)

3.0

3.5

4.0

4.5

5.0

-0.04

-0.02

0.00

0.02

0.04

Line Regulation(VOUT = 1.8V; IOUT = 1A)

Input Voltage (V)

VO

UT E

rro

r (%

)

-0.40

-0.30

-0.20

-0.10

0.00

0.10

0.20

0.30

0.40

2.7 2.9 3.1 3.3 3.5 3.7 3.9 4.1 4.3 4.5 4.7 4.9 5.1 5.3 5.5

Light Load Switching Waveform (VIN = 3.6V; VOUT = 1.8V; IOUT = 1mA; CFF = 0pF)

Time (5µs/div)

Out

put V

olta

ge (A

C c

oupl

ed)

(top)

(mV)

Inductor Ripple C

urrent(bottom

) (A)

-40

0

40

80

-0.1

0.0

0.1

0.2

0.3


Time (200µs/div)

Out

put V

olta

ge (A

C c

oupl

ed)

(top)

(mV)

Inductor Ripple C

urrent(bottom

) (A)

-80

-40

0

40

80

-0.1

0.0

0.1

0.2

0.3


Time (5µs/div)

Out

put V

olta

ge (A

C c

oupl

ed)

(top)

(mV)

Inductor Ripple C

urrent(bottom

) (A)

-40

0

40

80

-0.1

0.0

0.1

0.2

0.3


Time (500µs/div)

Out

put V

olta

ge (A

C c

oupl

ed)

(top)

(mV)

Inductor Ripple C

urrent(bottom

) (A)

-40

0

40

80

-0.1

0.0

0.1

0.2

8


DATA SHEET



Enable Soft Start(VIN = 3.6V; VOUT = 1.8V; IOUT = 1.7A)

Time (100µs/div)

VOUT

(1V/div)

EN

(2V/div)

IIN(500mA/div)

Heavy Load Switching Waveform (VIN = 3.6V; VOUT = 1.8V; IOUT = 1.7A)

Time (500ns/div)

Out

put V

olta

ge (A

C c

oupl

ed)

(top)

(mV)

Inductor Ripple C

urrent(bottom

) (A)

-20

-10

0

10

20

1.2

1.4

1.6

1.8

2.0

9


DATA SHEET




Output Current (mA)

Eff

icie

ncy (

%)

30

40

50

60

70

80

90

100

0.1 1 10 100 1000

VIN = 3.6V

VIN = 4.2V

VIN = 5V

Load Regulation(VOUT = 3.3V)

Output Current (mA)

Ou

tpu

t E

rro

r (%

)

-1

-0.8

-0.6

-0.4

-0.2

0

0.2

0.4

0.6

0.8

1

0.1 1 10 100 1000

VIN = 3.6V

VIN = 4.2V

VIN = 5V


Output Current (mA)

Eff

icie

ncy (

%)

30

40

50

60

70

80

90

100

0.1 1 10 100 1000

VIN = 3V

VIN = 3.6V

VIN = 4.2V

VIN = 5V


Output Current (mA)

Ou

tpu

t E

rro

r (%

)

-1

-0.8

-0.6

-0.4

-0.2

0

0.2

0.4

0.6

0.8

1

0.1 1 10 100 1000

VIN = 3V

VIN = 3.6V

VIN = 4.2V

VIN = 5V


Output Current (mA)

Eff

icie

ncy (

%)

30

40

50

60

70

80

90

100

0.1 1 10 100 1000

VIN = 2.7V

VIN = 3.6V

VIN = 4.2V


Output Current (mA)

Ou

tpu

t E

rro

r (%

)

-1

-0.8

-0.6

-0.4

-0.2

0

0.2

0.4

0.6

0.8

1

0.1 1 10 100 1000

VIN = 2.7V

VIN = 3.6V

VIN = 4.2V

10


DATA SHEET



Line Regulation(VOUT = 1.8V)

Input Voltage (V)

Accu

racy (

%)

-0.5

-0.4

-0.3

-0.2

-0.1

0

0.1

0.2

0.3

0.4

0.5

2.7 3.1 3.5 3.9 4.3 4.7 5.1 5.5

1mA

400mA

600mA

800mA

Switching Frequency vs. Temperature(VOUT = 1.8V; IOUT = 800mA)

Temperature (°C)

Sw

itch

ing

Fre

qu

en

cy (

MH

z)

1.92

1.94

1.96

1.98

2

2.02

2.04

2.06

2.08

-40 -15 10 35 60 85

Frequency Variation vs. Input Voltage

Input Voltage (V)

Fre

qu

en

cy V

ari

ati

on

(%

)

-4

-3

-2

-1

0

1

2

3

4

2.7 3.1 3.5 3.9 4.3 4.7 5.1 5.5

VOUT = 1.8V

VOUT = 3V

Output Voltage Error vs. Temperature(VIN = 3.6V; VO = 1.8V, IOUT = 400mA)

Temperature (°C)

Ou

tpu

t V

olt

ag

e E

rro

r (%

)

-2.0

-1.0

0.0

1.0

2.0

-40 -20 0 20 40 60 80 100

No Load Quiescent Current vs. Input Voltage

Input Voltage (V)

Su

pp

ly C

urr

en

t (µ

A)

10

15

20

25

30

35

40

45

50

55

60

2.7 3.1 3.5 3.9 4.3 4.7 5.1 5.5

85°C

25C

-40°C

P-Channel RDS(ON) vs. Input Voltage

Input Voltage (V)

RD

S(O

N) (m

ΩΩ)

200

250

300

350

400

450

500

550

2.5 3 3.5 4 4.5 5 5.5 6

120°C

100°C

85°C

25°C

11


DATA SHEET



N-Channel RDS(ON) vs. Input Voltage

Input Voltage (V)

RD

S(O

N) (m

ΩΩ)

200

250

300

350

400

450

500

550

2.5 3 3.5 4 4.5 5 5.5 6

120°C

100°C

85°C

25°C

Load Transient(VIN = 3.6V; VOUT = 1.8V; COUT = 10µF; CFF = 100pF)

Time (50µs/div)

Out

put V

olta

ge (t

op) (

V)

Output and Inductor C

urrent(100m

A/div)

1.7

1.8

1.9

300mA

1mA

300mA 1mA

Load Transient(VIN = 3.6V; VOUT = 1.8V; COUT = 4.7µF; CFF = 0pF)

Time (50µs/div)

Out

put V

olta

ge (t

op) (

V)


urrent(100m

A/div)

1.7

1.8

1.9

400mA

300mA

400mA300mA


Time (50µs/div)

Out

put V

olta

ge (t

op) (

V)


urrent(100m

A/div)

1.7

1.8

1.9

400mA

400mA

300mA

300mA


Time (50µs/div)

Out

put V

olta

ge (t

op) (

V)


urrent(100m

A/div)

1.7

1.8

1.9

400mA

300mA

400mA

300mA

Line Transient(VOUT = 1.8V; VIN = 3.6V to 4.2V; IOUT = 400mA; CFF = 0pF)

Time (50µs/div)

Inpu

t Vol

tage

(top

) (V)

Output Voltage (bottom

) (V)

3

3.6

4.2

4.8

1.76

1.78

1.8

1.82

1.84

12


DATA SHEET



Output Ripple(VOUT = 1.8V; VIN = 3.6V; IOUT = 1mA; CFF = 0pF)

Time (10µs/div)

Out

put V

olta

ge (t

op) (

V) Inductor Current

(bottom) (A

)

-0.01

0

0.01

0.02

-0.05

0

0.05

0.1

Output Ripple(VOUT = 1.8V; VIN = 3.6V; IOUT = 400mA; CFF = 0pF)

Time (200ns/div)

Out

put V

olta

ge (t

op) (

V) Inductor Current

(bottom) (A

)

-0.02

-0.01

0

0.01

0.02

-0.2

0

0.2

0.4

0.6

Soft Start(VIN = 3.6V; VOUT = 1.8V; IOUT = 400mA)

Time (100µs/div)

En

ab

le V

olt

ag

e (

top

) (V

)

Ou

tpu

t V

olt

ag

e (

mid

dle

) (V

) Inp

ut C

urre

nt (b

otto

m) (A

)

0

1

2

3

4

-0.5

0

0.5

13


DATA SHEET


Functional DescriptionThe AAT2789 is a 2-channel synchronous step-down (Buck) converter operating from an input voltage range of 2.7V to 5.5V; making it the ideal choice for single-cell Lithium-ion/polymer battery powered systems or low voltage 3.3V and 5V based consumer equipment.

Channel 1 delivers up to 1700mA output current while Channel 2 delivers up to 800mA. Both converters incor-porate a unique low noise architecture which reduces output ripple and spectral noise.

The device utilizes a high switching frequency to mini-mize external filter sizing. Peak current mode control eliminates external compensation while optimizing tran-sient performance and stability.

The device requires a minimum of external components to realize a high efficiency dual-output step-down con-verter while minimizing solution size and footprint.

Each of the step-down regulators has an independent input and enable pin. Adjustable output voltage is pro-vided. Light load operating mode provides high efficiency over the entire load range. The enable inputs, when pulled low, force the respective converter into a low power non-switching state consuming less than 1μA of current. Low quiescent current enables excellent life for battery powered systems.

Additional features include integrated soft start to limit inrush current. Soft start limits the current surge seen at the input and eliminates output voltage overshoot.

For overload conditions, the peak input current is limit-ed. Also, over-temperature protection safeguards the device from damage due to high operating temperature or fault conditions. The junction over-temperature threshold is 140°C with 15°C of hysteresis. Under volt-age lockout (UVLO) guarantees sufficient input voltage bias prior to turn-on.

The AAT2789 is available in the 3x4mm Pb-free 16-pin TDFN package and is rated over the -40°C to 85°C oper-ating temperature range.

Functional Block Diagram

Logic

ErrorAmp

Control Logic

Comp.

VP1

LX1

PGND1

FB1

EN1

Logic

ErrorAmp

Control Logic

Comp.

VP2

LX2

PGND2

FB2

EN2

AGND1,2

OSCOT

VoltageRef 1

VoltageRef 2

VCC1,2

OSCOT

14


DATA SHEET


Applications Information

Inductor SelectionBoth step-down converters use peak current mode con-trol with slope compensation to maintain stability for duty cycles greater than 50%. When the duty cycle exceeds 50%, the inductor value must be selected to maintain the prescribed down-slope in accordance with the internal slope compensation requirements.

Channel 1The internal slope compensation for the adjustable and low voltage fixed versions of Channel 1 is 0.75A/μs. This equates to a slope compensation that is 75% of the inductor current down slope for a 1.8V output and 1.8μH inductor.

0.75 ⋅ VO m = = = 0.75

L

0.75 ⋅ 1.8V

1.8µH

A

µs

0.75 ⋅ VO L = = = 1.2µH

m

0.75 ⋅ 1.2V

0.75 A

µs

The inductor should be set equal to the output voltage numeric value in microhenries (μH). This guarantees suf-ficient internal slope compensation. Manufacturer’s spec-ifications list both the inductor DC current rating, which is a thermal limitation, and the peak current rating, which is determined by the saturation characteristics. The inductor should not show any appreciable saturation under normal load conditions. Some inductors may meet the peak and average current ratings yet result in exces-sive losses due to a high DCR. Always consider the losses associated with the DCR and its effect on the total converter efficiency when selecting an inductor.

Channel 2The slope compensation for Channel 2 output is set at 0.75A/μs. This equates to a slope compensation that is 75% of the inductor current down slope for a 1.8V out-put and 1.8μH inductor:

0.75 ⋅ VO m = = = 0.75

L

0.75 ⋅ 1.8V

1.8µH

A

µs

0.75 ⋅ VO L = = = 3.3µH

m

0.75 ⋅ 3.3V

0.75 A

µs

Input CapacitorSelect a 10μF to 22μF X7R or X5R ceramic capacitor for the input. To estimate the required input capacitor size, determine the acceptable input ripple level (VPP) and solve for CIN. The calculated value varies with input volt-age and is a maximum when VIN is double the output voltage.

⎛ ⎞ · 1 - ⎝ ⎠

VO

VIN

CIN =

VO

VIN

⎛ ⎞ - ESR · FS⎝ ⎠

VPP

IO

⎛ ⎞ · 1 - = for VIN = 2 · VO⎝ ⎠VO

VIN

VO

VIN

1

4

CIN(MIN) =

1

⎛ ⎞ - ESR · 4 · FS⎝ ⎠

VPP

IO

Always examine the ceramic capacitor DC voltage coef-ficient characteristics when selecting the proper value. For example, the capacitance of a 10μF, 6.3V, X5R ceram-ic capacitor with 5.0V DC applied is actually about 6μF.

The maximum input capacitor RMS current is:

⎛ ⎞IRMS = IO · · 1 - ⎝ ⎠

VO

VIN

VO

VIN

The input capacitor RMS ripple current varies with the input and output voltage and will always be less than or equal to half of the total DC load current.

⎛ ⎞· 1 - = D · (1 - D) = 0.52 =

⎝ ⎠VO

VIN

VO

VIN

1

2

For VIN = 2 · VO

IO

RMS(MAX)I

2=

The term ⎛ ⎞

· 1 - ⎝ ⎠VO

VIN

VO

VIN appears in both the input voltage ripple and input capacitor RMS current equations and is a maximum when VO is twice VIN. This is why the input voltage ripple and the input capacitor RMS current ripple are a maximum at 50% duty cycle.

15


DATA SHEET


The input capacitor provides a low impedance loop for the edges of pulsed current drawn by the AAT2789. Low ESR/ESL X7R and X5R ceramic capacitors are ideal for this function. To minimize stray inductance, the capaci-tor should be placed as closely as possible to the IC. This keeps the high frequency content of the input current localized, minimizing EMI and input voltage ripple. The proper placement of the input capacitor (C1) can be seen in the evaluation board layout in the Layout section of this datasheet (see Figures 1 and 2).

A laboratory test set-up typically consists of two long wires running from the bench power supply to the eval-uation board input voltage pins. The inductance of these wires, along with the low-ESR ceramic input capacitor, can create a high Q network that may affect converter performance. This problem often becomes apparent in the form of excessive ringing in the output voltage dur-ing load transients. Errors in the loop phase and gain measurements can also result. Since the inductance of a short PCB trace feeding the input voltage is significantly lower than the power leads from the bench power sup-ply, most applications do not exhibit this problem.

In applications where the input power source lead induc-tance cannot be reduced to a level that does not affect the converter performance, a high ESR tantalum or alu-minum electrolytic should be placed in parallel with the low ESR/ESL bypass ceramic capacitor. This dampens the high Q network and stabilizes the system.

Output Capacitor

Channel 1The output capacitor limits the output ripple and pro-vides holdup during large load transitions. A 10μF to 22μF X5R or X7R ceramic capacitor typically provides sufficient bulk capacitance to stabilize the output during large load transitions and has the ESR and ESL charac-teristics necessary for low output ripple.

The output voltage droop due to a load transient is dominated by the capacitance of the ceramic output capacitor. During a step increase in load current, the ceramic output capacitor alone supplies the load current until the loop responds. Within two or three switching cycles, the loop responds and the inductor current increases to match the load current demand. The rela-tionship of the output voltage droop during the three switching cycles to the output capacitance can be esti-mated by:

COUT = 3 · ΔILOAD

VDROOP · FS

Once the average inductor current increases to the DC load level, the output voltage recovers. The above equa-tion establishes a limit on the minimum value for the output capacitor with respect to load transients.

The internal voltage loop compensation also limits the minimum output capacitor value to 10μF. This is due to its effect on the loop crossover frequency (bandwidth), phase margin, and gain margin. Increased output capac-itance will reduce the crossover frequency with greater phase margin.

The maximum output capacitor RMS ripple current is given by:

1

2 3RMS(MAX)I

L · FS · VIN(MAX)

= · ·

VOUT · (VIN(MAX) - VOUT)

Dissipation due to the RMS current in the ceramic output capacitor ESR is typically minimal, resulting in less than a few degrees rise in hot-spot temperature.

Channel 2The output capacitor limits the output ripple and pro-vides holdup during large load transitions. A 4.7μF to 10μF X5R or X7R ceramic capacitor typically provides sufficient bulk capacitance to stabilize the output during large load transitions and has the ESR and ESL charac-teristics necessary for low output ripple.

Output VoltageThe AAT2789 output voltages are programmed with external resistors R1, R2 (Channel 1) and R3, R4 (Channel 2). To limit the bias current required for the external feed-back resistor string while maintaining good noise immu-nity, the minimum suggested value for R2 and R4 are 59kΩ. Although a larger value will further reduce quies-cent current, it will also increase the impedance of the feedback node, making it more sensitive to external noise and interference. Table 1 summarizes the resistor values for various output voltages with R2 and R4 set to either 59kΩ for good noise immunity or 221kΩ for reduced no load input current.

16


DATA SHEET


VOUT(V)R2, 4 = 59k

R1, 3(k)R2, 4 = 221k

R1, 3(k)0.6 0 00.8 19.6 75.00.9 29.4 1131.0 39.2 1501.1 49.9 1871.2 59.0 2211.3 68.1 2611.4 78.7 3011.5 88.7 3321.8 118 4421.85 124 4642.0 137 5232.5 187 7153.0 237 8873.3 267 1000

Table 1: AAT2789 Resistor Values for Various Output Voltages.

Thermal CalculationsThere are three types of losses associated with the AAT2789 step-down converter: switching losses, con-duction losses, and quiescent current losses. Conduction losses are associated with the RDS(ON) characteristics of the power output switching devices. Switching losses are dominated by the gate charge of the power output switching devices. At full load, assuming continuous con-duction mode (CCM), a simplified form of both step-down converters is given by:

PTOTAL

IO1

2 · (RDSON(HS) · VO1 + RDSON(L) · [VIN -VO1])

VIN1

= + (tsw · FS · IO1 + IQ1) · VIN1

+ + (tsw · FS · IO2 + IQ2) · VIN2

IO2

2 · (RDSON(HS) · VO2 + RDSON(L) · [VIN -VO2])

VIN2

IQ1 and IQ2 are the step-down converter quiescent cur-rents for Channel 1 and Channel 2 respectively. The term tSW is used to estimate the full load step-down converter switching losses.

For the condition where the step-down converter is in dropout at 100% duty cycle, the total device dissipation reduces to:

PTOTAL = IO1

2 · RDS(ON)H1 + IQ1 · VIN1 + IO2

2 · RDS(ON)H2 + IQ2 · VIN2

Since RDS(ON), quiescent current, and switching losses all vary with input voltage, the total losses should be inves-tigated over the complete input voltage range.

Given the total losses, the maximum junction tempera-ture can be derived from the θJA for the TDFN34-16 package, which is 50°C/W.

TJ(MAX) = PTOTAL · ΘJA + TAMB

PCB LayoutThe suggested PCB layout for the AAT2789 is shown in Figures 1 and 2. The following guidelines should be used to help ensure a proper layout.

1. The input and output capacitors C1, C2, C3, and C4 should be connected as closely as possible to the input and output pins.

2. Output capacitors and inductors (C2, C3 and L1; C4 and L2) should connect as closely as possible. The connection of the inductor (L1, L2) to the LX1 and LX2 pins should be as short as possible.

3. The feedback traces or FB pins should be separated from any power traces and connect as closely as possible to the load point. Sensing along a high-current load trace will degrade DC load regulation.

4. The resistance of the trace from the load return to PGND should be kept to a minimum. This will help to minimize any error in DC regulation due to differ-ences in the potential of the internal signal ground and the power ground.

5. The lower R2 (FB1) and R4 (FB2) resistor's grounds should be connected to the AGND1 and AGND2 pins.

6. C5, C6 are optional feed forward capacitors for both channels to stabilize the output voltage during large load transitions.

7. For good thermal coupling, PCB vias are required from the pad for the TDFN paddle to the bottom ground plane.

17


DATA SHEET


Printed Circuit Board Layout Recommendations

Figure 1: AAT2789 Evaluation Board Figure 2: AAT2789 Evaluation Board Component Side Layout. Solder Side Layout.

optC6

59KR4

59KR2

59KR1

267KR3

VIN

OUT2

OUT1

optC5

10μFC4

10μFC2

PGND22

LX23

VP24

VCC15

VP18

NC1

EN16

VP17

LX19

PGND1 10

FB111

AGND112

VCC213

EN214

FB2 15

AGND2 16

AAT2789

TDFN34-16

U1

1.5μH

L1

3.3μH

L2

10μFC3

10μFC1

Figure 3: AAT2789 Evaluation Board Schematic.

Symbol Part Number Description QtyU1 AAT2789 Skyworks 2-Output Buck TDFN34-16 1

C1, C2, C3, C4 GRM188R60J106ME47D Cap, MLC, 10uF/6.3V, 0603 ( HMAX=0.9mm), Murata 4C5 Generic Cap,10nF/6.3V,0402 1C6 Generic Cap,100pF/6.3V,0402 1L1 LQM2HPN1R5MG0 1.5uH, ISAT=3A, 2x2.5x0.9mm (HMAX=0.95mm), shielded chip inductor, Murata 1L2 TFC252008MBT 3.3uH, ISAT=0.52A, 2x2.5x1mm (HMAX=1.0mm), non-shielded chip inductor, TDK 1

R1-R4 Generic Carbon Film resistor, 0402 1

Table 2: AAT2789 Evaluation Board Bill of Materials.

18


DATA SHEET


Design Example

SpecificationsVO1 = 1.2V @ 1.5A (adjustable using 0.6V version), Pulsed Load ILOAD = 1.5AVO2 = 3.3V @ 500mA (adjustable using 0.6V version), Pulsed Load ILOAD = 0.5AVIN = 2.7V to 4.2V (3.6V nominal)FS1 = 1.8MHz, FS2 = 2MHzm = 0.75A/μsTAMB = 85°C in TDFN34-16 Package

Channel 1 Inductor

0.75 ⋅ VO L = = = 1.2µH; use 1.5µH

m

0.75 ⋅ 1.2V

0.75 A

µs

For TDK inductor LQM2PHN1R5MG0, 1.5μH, DCR = 70mmax.

ΔI = · 1 - = · 1 - = 317mA

IPK1 = IO1 + = 1.5A + 0.317A = 1.817A

PL1 = IOUTBUCK

2 ⋅ DCR = 1.5A

2 ⋅ 70mΩ = 158mW

⎛⎝

⎞⎠

⎛⎝

⎞⎠

VO1

L1 ⋅ FS

ΔI

2

VO1

VIN

1.2V

4.2V

1.2V

1.5µH ⋅ 1.8MHz

Channel 2 Inductor

0.75 ⋅ VO L = = = 3.3µH

m

0.75 ⋅ 3.3V

0.75 A

µs

For TDK inductor TFC252008MBT, 3.3μH, DCR = 100mmax.

ΔI = · 1 - = · 1 - = 107mA

IPK1 = IO1 + = 0.5A + 0.054A = 0.55A

PL1 = IOUTBUCK

2 ⋅ DCR = 0.55A

2 ⋅ 100mΩ = 30.1mW

⎛⎝

⎞⎠

⎛⎝

⎞⎠

VO1

L1 ⋅ FS

ΔI

2

VO2

VIN

3.3V

4.2V

3.3V

3.3µH ⋅ 1.8MHz

19


DATA SHEET


Channel 1 Output CapacitorVDROOP= 0.12V

1

2 3

1 1.2V · (4.2V - 1.2V)

1.5µH · 1.8MHz · 4.2V 2 3RMS(MAX)I

L · FS · VIN(MAX)

= · ·

3 · ΔILOAD

VDROOP · FS

3 · 1.5A

0.12V · 1.8MHzCOUT3 = = = 20.8µF; use 22µF

· = 92mA·

VOUT · (VIN(MAX) - VOUT)=

PESR = ESR · IRMS2 = 5mΩ · 24mA2 = 3µW

Channel 2 Output CapacitorVDROOP= 0.1V

1

2 3

1 3.3V · (4.2V - 3.3V)

3.3µH · 2MHz · 4.2V 2 3RMS(MAX)I

L · FS · VIN(MAX)

= · ·

3 · ΔILOAD

VDROOP · FS

3 · 0.5A

0.1V · 2MHzCOUT3 = = = 7.5µF; use 10µF

· = 30mA·

VOUT · (VIN(MAX) - VOUT)=

PESR = ESR · IRMS2 = 5mΩ · 30mA2 = 4.5µW

Input CapacitorInput Ripple VPP1 = 50mV, VPP2 = 25mV

CIN1 = = = 4.9µF

1

⎛ ⎞- ESR · 4 · FS⎝ ⎠

VPP1

IO1

1

⎛ ⎞ - 5mΩ · 4 · 1.8MHz

⎝ ⎠50mV

1.5A

CIN2 = = = 3µF

1

⎛ ⎞- ESR · 4 · FS⎝ ⎠

VPP2

IO2

1

⎛ ⎞ - 5mΩ · 4 · 2MHz

⎝ ⎠25mV

0.5A

CIN = CIN1+ CIN2 = 4.9μF+3μF= 7.9μF; use 10μF

IO1 + IO2

2RMS(MAX)I

P = ESR · IRMS

2 = ESR · (1A)

2 = 5mW

= = 1A

20


DATA SHEET


AAT2789 LossesTotal loss can be estimated by calculating the dropout (VIN = VO) losses where the power MOSFETs RDS (ON) will be at the maximum value. All values assume an 85°C ambient temperature and a 120°C junction temperature with the TDFN 50°C/W package.

PTOTAL = IO1

2 · RDS(ON)H1 + IQ1 · VIN1 + IO2

2 · RDS(ON)H2 + IQ2 · VIN2

PTOTAL = 1.5A2 · 120mΩ + 70µA · 4.2 + 0.5

2 · RDS(ON)H2 + 70µA · 4.2V = 270mW

TJ(MAX)= TAMB + ΘJA · PLOSS = 85°C + (50°C/W) · 270mW = 99°C

21


DATA SHEET


Ordering Information

PackageOutput Voltage

Marking1 Part Number (Tape and Reel)2Channel 1 Channel 2TDFN34-16 Adjustable (0.6) Adjustable (0.6) 3JXYY AAT2789IRN-AA-T1

Skyworks Green™ products are compliant with all applicable legislation and are halogen-free.For additional information, refer to Skyworks Definition of Green™, document number SQ04-0074.

Legend Output Voltage Code Adjustable (0.6) A

1. XYY = assembly and date code.2. Sample stock is generally held on part numbers listed in BOLD.

22


DATA SHEET


Copyright © 2012 Skyworks Solutions, Inc. All Rights Reserved.

Information in this document is provided in connection with Skyworks Solutions, Inc. (“Skyworks”) products or services. These materials, including the information contained herein, are provided by Skyworks as a service to its customers and may be used for informational purposes only by the customer. Skyworks assumes no responsibility for errors or omissions in these materials or the information contained herein. Sky-works may change its documentation, products, services, specifi cations or product descriptions at any time, without notice. Skyworks makes no commitment to update the materials or information and shall have no responsibility whatsoever for confl icts, incompatibilities, or other diffi culties arising from any future changes.

No license, whether express, implied, by estoppel or otherwise, is granted to any intellectual property rights by this document. Skyworks assumes no liability for any materials, products or information provided here-under, including the sale, distribution, reproduction or use of Skyworks products, information or materials, except as may be provided in Skyworks Terms and Conditions of Sale.

THE MATERIALS, PRODUCTS AND INFORMATION ARE PROVIDED “AS IS” WITHOUT WARRANTY OF ANY KIND, WHETHER EXPRESS, IMPLIED, STATUTORY, OR OTHERWISE, INCLUDING FITNESS FOR A PARTICULAR PURPOSE OR USE, MERCHANTABILITY, PERFORMANCE, QUALITY OR NON-INFRINGEMENT OF ANY INTELLECTUAL PROPERTY RIGHT; ALL SUCH WARRANTIES ARE HEREBY EXPRESSLY DISCLAIMED. SKYWORKS DOES NOT WARRANT THE ACCURACY OR COMPLETENESS OF THE INFORMATION, TEXT, GRAPHICS OR OTHER ITEMS CONTAINED WITHIN THESE MATERIALS. SKYWORKS SHALL NOT BE LIABLE FOR ANY DAMAGES, IN-CLUDING BUT NOT LIMITED TO ANY SPECIAL, INDIRECT, INCIDENTAL, STATUTORY, OR CONSEQUENTIAL DAMAGES, INCLUDING WITHOUT LIMITATION, LOST REVENUES OR LOST PROFITS THAT MAY RESULT FROM THE USE OF THE MATERIALS OR INFORMATION, WHETHER OR NOT THE RECIPIENT OF MATERIALS HAS BEEN ADVISED OF THE POSSIBILITY OF SUCH DAMAGE.

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Skyworks, the Skyworks symbol, and “Breakthrough Simplicity” are trademarks or registered trademarks of Skyworks Solutions, Inc., in the United States and other countries. Third-party brands and names are for identifi cation purposes only, and are the property of their respective owners. Additional information, including relevant terms and conditions, posted at www.skyworksinc.com, are incorporated by reference.

Package Information1

TDFN34-16

3.000 ± 0.050 1.600 ± 0.050

0.050 ± 0.050 0.229 ± 0.051

(4x)

0.85

0 M

AX

4.00

0 ±

0.05

0

3.30

0 ±

0.05

0

Index AreaDetail "A"

Top View Bottom View

Side View

0.350 ± 0.100

0.23

0 ±

0.05

00.

450

± 0.

050

Detail "A"

Pin 1 Indicator(optional)

C0.3

All dimensions in millimeters.

1. The leadless package family, which includes QFN, TQFN, DFN, TDFN and STDFN, has exposed copper (unplated) at the end of the lead terminals due to the manufacturing process. A solder fillet at the exposed copper edge cannot be guaranteed and is not required to ensure a proper bottom solder connection.

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