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Abstract
Sabol, Dušan: WDM systémy s DPSK kľúčovaním [Diplomová práca]. Žilinská
univerzita v Žiline. Elektrotechnická fakulta; Katedra telekomunikácií. Školiteľ: Ing.
Jozef Dubovan. Stupeň odbornej kvalifikácie: inžinier (Ing.). Žilina: EF ŽU, 2006. 51 s.
Complex approach to optical communication is proposed in my work, where
limitation factors due to significant physical phenomena with cancellation techniques and
their suitability investigated. Economical fundamental factors are also involved following
trends in optical communication are proposed. Frequently used DPSK format is
theoretically described and impact of OSNR level and laser linewidth on its performance
is investigated by simulation technique provided in VPI simulation software. Behavior of
used modulation format within WDM system examined at four channel’s WDM and
affect of Kerr effect is qualitatively assessed.
Key words: DPSK, DQPSK, OOK, FWM, WDM, BER, limitation factors
ANOTAČNÝ ZÁZNAM - DIPLOMOVÁ PRÁCA
Priezvisko, meno: Sabol, Dušan školský rok: 2005/2006
Názov práce: WDM systémy s DPSK kĺúčovaním
Počet strán: 51 Počet obrázkov: 46 Počet tabuliek: 1
Počet grafov: 0 Počet príloh: 0 Použitá lit.: 17
Anotácia (slov. resp. český jazyk): Táto diplomová práca skúma limitujúce faktory
dnešných WDM sytémov. Popis DPSK modulácie a jej aplikácii, ako budúceho
modulačného formátu pre optické komunikácie ďalšej generácie. Práca obsahuje
simulácie popisujúce chybovosť jednotlivých typov modulácii a následne ich poškodenia
pôsobením Kerrovho efektu v štovkanálovom WDM systéme.
Anotácia v cudzom jazyku (anglický resp. nemecký): This diploma thesis investigates
limitation factors of current WDM systems. Description of DPSK modulation and its
applications as modulation format for optical communication of next generation. Thesis
contains simulation that describes BER of selected modulations and their distortions due
to Kerr effect at four channel WDM system.
Kľúčové slová: DPSK, DQPSK, OOK, FWM, WDM, BER, Limitujúce faktory
Vedúci práce: Ing. Jozef Dubovan
Recenzent práce: Prof. Ing. Milan Dado, PhD.
Dátum odovzdania práce: 19.5.2006
I
Content
List of Figures and Tables .........................................................................................III
List of Abbreviations .........................................................................................................VI
1 Introduction..................................................................................................................1
2 Complex approach to optical communication .............................................................2
2.1 Physical characteristic..........................................................................................2
2.2 Mitigation of impairments and distortions...........................................................3
2.2.1 Nonlinear effects..........................................................................................3
2.2.1.1 Kerr effect ................................................................................................3
2.2.1.2 Stimulated scatterings ..............................................................................7
2.2.2 Amplification ...............................................................................................9
2.2.3 Shaping ......................................................................................................12
2.2.4 Jitter............................................................................................................16
2.3 Modulation format .............................................................................................17
2.4 Economical aspects............................................................................................18
2.4.1 Catalysts of OT ..........................................................................................18
2.4.2 Inhibitors of OT .........................................................................................20
3 Differential phase-shift keyed format ........................................................................21
3.1 DPSK format......................................................................................................21
3.2 DPSK transmitter ...............................................................................................23
3.2.1 Transmitter evaluation ...............................................................................24
3.2.2 Pulse carver................................................................................................24
3.3 DPSK Receiver ..................................................................................................26
3.3.1 Balanced versus single-ended detection ....................................................27
3.3.2 Tolerance to Optical Filtering....................................................................29
3.4 DPSK transmission at 10 Gb/s...........................................................................30
3.5 DPSK transmission at 40 Gb/s...........................................................................31
3.6 DQPSK application............................................................................................32
4 Trends in the optical communication.........................................................................34
4.1 Transmission bands and spectral efficiency ......................................................34
4.2 Multiplexing techniques.....................................................................................34
4.2.1 Time division multiplex (OTDM) .............................................................34
II
4.2.2 Wavelength Division Multiplex.................................................................35
4.3 Simulation ..........................................................................................................35
4.3.1 DQPSK format...........................................................................................35
4.3.2 DPSK format..............................................................................................38
4.3.3 OOK format ...............................................................................................40
4.4 Impact of Kerr effect..........................................................................................40
4.4.1 Description of simulation scheme..............................................................40
4.4.2 OOK performance......................................................................................42
4.4.3 DPSK performance ....................................................................................44
4.4.4 DQPSK performance .................................................................................46
4.4.5 Potential of best setup ................................................................................48
5 Conclusion .................................................................................................................51
III
LIST OF FIGURES AND TABLES FIGURE 1: SPECTRAL VARIATION OF ATTENUATION; SOURCE [1]..........................................2
FIGURE 2: PRODUCTS OF KERR EFFECT; [6]. .........................................................................4
FIGURE 3: A) TEMPORAL VARIATION OF SPM-INDUCED PHASE SHIFT AND FREQUENCY CHIRP
FOR GAUSSIAN (DASHED CURVE) AND SUPER-GAUSSIAN (SOLID CURVE) PULSE. B)
EXPERIMENTALLY OBSERVED SPECTRA FOR A NEARLY GAUSSIAN PULSE AT THE
OUTPUT OF A 99 M LONG FIBRE. SPECTRA ARE LABELED BY MAXIMUM PHASE SHIFT
RELATED LINEARLY TO THE PEAK POWER; [4]. ..............................................................5
FIGURE 4: EYE DIAGRAM OF COMPLETE AND INCOMPLETE COLLISIONS; [5]..........................5
FIGURE 5: A) NONLINEAR CROSSTALK DUE TO FWM, B) EYE DIAGRAM OF AMPLITUDE NOISE
DUE TO FWM; [5]. ........................................................................................................6
FIGURE 6: EXAMPLES OF INTRACHANNEL EFFECTS; [7]. ........................................................7
FIGURE 7: RAMAN GAIN COEFFICIENT FOR PURE SILICA AND 1550 NM PUMP WAVELENGTH;
[8]. ................................................................................................................................8
FIGURE 8: THE OUTCOME OF SRS AT WDM SYSTEM; [5]. ....................................................8
FIGURE 9: BEHAVIOR OF INPUT AND OUTPUT POWER DUE TO SBS; [5]. ................................9
FIGURE 10: CHARACTERISTIC OF ERBIUM AMPLIFIER (LEFT) AND RAMAN AMPLIFIER
(RIGHT); [7].................................................................................................................11
FIGURE 11: VARIOUS HYBRID AMPLIFICATION SCHEMES; [7]. .............................................12
FIGURE 12: THE DISPERSION’S INFLUENCE; [7]. ..................................................................13
FIGURE 13: MATERIAL, WAVEGUIDE AND CHROMATIC DISPERSION FOR CURRENT FIBRES; .13
FIGURE 14: DISPERSION COMPENSATION BY FBG; [9]. .......................................................14
FIGURE 15: A), C) SYMMETRICAL DISPERSION MANAGEMENT; B), D) NON SYMMETRICAL
DISPERSION MANAGEMENT; [5]. ..................................................................................15
FIGURE 16: THE EFFECT OF DISPERSION SLOPE FOR BORDER AND CENTRAL FREQUENCIES;
[5]. ..............................................................................................................................15
FIGURE 17: PMD DUE TO BIREFRINGENCE EFFECT; [11]. ....................................................16
FIGURE 18: CANCELLATION OF TIMING JITTER WITH SYMMETRIC DISPERSION PROFILE; [5].
....................................................................................................................................17
FIGURE 19: COMPARISON OF IP TRAFFIC PREDICTIONS WITH INSTALLED CAPACITY; [1].....19
FIGURE 20: SIGNAL CONSTELLATION OF OOK AND DPSK MODULATION; [16] ..................22
FIGURE 21: TYPICAL DPSK TRANSMITTERS: A) IMPLEMENTATION WITH PM, B)
IMPLEMENTATION WITH MZM; [16] ...........................................................................24
IV
FIGURE 22: A) A TYPICAL RZ-DPSK TRANSMITTER. (B) OPTICAL INTENSITY AND PHASE
WAVEFORMS GENERATED BY AN IMPERFECT PULSE CARVER; [16]. .............................25
FIGURE 23: DPSK RECEIVER; [16]. .....................................................................................26
FIGURE 24: NUMERICAL CALCULATIONS FOR THE REQUIRED OSNR AT BER = 10-10 FOR
33% RZ-DPSK AND OOK AS A FUNCTION OF RECEIVER AMPLITUDE IMBALANCE Β;
[16].............................................................................................................................28
FIGURE 25: PENALTIES IN NON IDEAL RZ-DPSK RECEIVERS: (A) AMPLITUDE IMBALANCE IN
THE BALANCED DETECTOR (DASHED CURVE IS FOR A DELAY INTERFEROMETER WITH
AN EXTINCTION RATIO OF ONLY 10 DB), (B) PHASE IMBALANCE IN THE BALANCED
DETECTOR, (C) DELAY-TO-BIT RATE MISMATCH IN THE DELAY INTERFEROMETER, (D)
LASER FREQUENCY OFFSET FROM THE IDEAL AS SET BY THE INTERFEROMETER PHASE
DIFFERENCE (DASHED CURVE IS FOR 33% RZ-DPSK). CIRCLES ARE EXPERIMENTAL
RESULTS; [16]. ............................................................................................................29
FIGURE 26: EXPERIMENTAL RESULTS OF PENALTIES FROM NARROW OPTICAL AND
ELECTRICAL FILTERING; [16] ......................................................................................29
FIGURE 27: DQPSK TRANSMITTER AND RECEIVER; [16]. ...................................................32
FIGURE 28: EXPERIMENTAL SETUP OF; [18]. .......................................................................36
FIGURE 29: SIMULATION SCHEME OF BER = ƒ (OSNR). .....................................................36
FIGURE 30: COMPARISON OF EXPERIMENTAL [18] AND SIMULATION OUTPUT.....................37
FIGURE 31: BER VS OSNR FOR 10 GB/S AND 40 GB/S DQPSK FORMAT. ..........................38
FIGURE 32: SIMULATION SCHEME OF BER = ƒ (OSNR). .....................................................39
FIGURE 33: BER VS OSNR FOR 10 GBS AND 40 GB/S DPSK FORMAT. ..............................40
FIGURE 34: SIMULATION SCHEME OF FWM GENERATION...................................................41
FIGURE 35: EYE DIAGRAM OF OOK TRANSMITTER, A) 2 MHZ LINEWIDTH, B) 500 KHZ
LINEWIDTH..................................................................................................................42
FIGURE 36: EYE DIAGRAM AFTER FIRST LOOP. ....................................................................43
FIGURE 37: SPECTRUM AFTER FIRST LOOP. .........................................................................43
FIGURE 38: DPSK BACK-TO-BACK EYE DIAGRAM OF A) 2 MHZ AND B) 500 KHZ LINEWIDTH
....................................................................................................................................44
FIGURE 39: DPSK EYE DIAGRAM AFTER THE FIRST LOOP....................................................45
FIGURE 40: DPSK SPECTRUM AFTER THE FIRST LOOP. ........................................................46
FIGURE 41: DQPSK EYE DIAGRAMS IN THE BACK-TO-BACK CONDITION A) 2 MHZ, B) 500
KHZ. ...........................................................................................................................47
FIGURE 42: DQPSK EYE DIAGRAM AFTER THE FIRST LOOP.................................................47
V
FIGURE 43: DQPSK SPECTRUM AFTER THE FIRST LOOP ......................................................48
FIGURE 44: DPSK EYE DIAGRAM AFTER FIRST LOOP...........................................................49
FIGURE 45: DPSK SPECTRUM AFTER FIRRST LOOP..............................................................49
FIGURE 46: SIGNAL POWER OF SELECTED CHANNELS RELATE ON THE NUMBER OF LOOP ....50
TABLE 1: PARAMETERS OF ULTRA HIGH SPEED ELECTRONICS; [16].....................................35
VI
List of Abbreviations
AMI Alternate-Mark Inversion ARMA Autoregresive Moving Average ASE Amplified Spontaneuos Emission ATM Asynchronous Transfer Mode AWGN Additive White Gaussian Noise B Channel bit rate BB Broad Band BER Bit Error Rate BoD Bandwidth on Demand CSRZ Carrier-Suppressed Return to Zero CT Communication Technologies CW Continuous Wave D Fibre Dispersion DBPSK Differential Binary Phase-Shift-Keyed DC Direct current DCF Dispersion Compensating Fibre DI Delay Interferometer DPSK Differential-Phase-Shift-Keyed DWDM Dense Wavelength Division Multiplex EDFA Erbium Doped Fibre Amplifier FBG Fibre Bragg Grating FEC Forwad Error Correction FTTx Fibre to the various structure FWM Four Wave Mixing HBT Heterojunction Bipolar Transistor HEMT High Electron Mobility Transistor iFWM Intra Four Wave Mixing IPoWDM IP over WDM IT Information Technologies iXPM Intra Cross Phase Modulation MA Moving Average MZM Mach-Zehnder Modulator NF Noise Figure NRZ Non Return to Zero NZ-DSF Non Zero - Dispersion Shifted Fibre OBS Optical Burst Switching OOK On-Off Keying OPS Optical Packet Switching OT Optical Communication OT Optical Technologies OTDM Optical Time Division Multiplex P0 Threshold Power PLC Planar-Lightwave-Circuit PM Phase Modulator
VII
PMD Polarization Mode Dispersion QoS Quality of Service RZ Return to Zero RZ-AMI Return to Zero Alternate-Mark Inversion RZ-DPSK Return to zero Differential-Phase-Shift-Keying RZ-Duobinary Return to Zero Duobinary SBS Stimulated Brillouin Scattering SDH Synchronous Digital Hierarchy SMF Single Mode Fibre SNR Signal to Noise Ratio SPM Self Phase Modulation SRS Stimulated Raman Scattering WDM Wavelength Division Multiplex xDSL various Digital Subscriber Line XPM Cross Phase Modulatio xPON various Passive Optical Network
Aeff Effective Core Area
|E|2 Optical Intensity Inside the Fibre
gB Peak Value of Brillouin-Gain Coefficient
gR Raman-Gain Coefficient
k0 Wave Number
k0i Wave Number of ith Carrier
L Fibre Length
Leff Effective Length
n (ω) Constant Part Given by Sellmeier Equation
n2 Nonlinear Refractive Index Coefficient Related to 3rd Order Susceptibility
β Propagation Constant
ΔnNL(i) Nonlinear Refractive Index of ith Wavelength in XPM
δω Frequency Chirp
ΦNL Nonlinear Phase Shift
ΦNL(i) Nonlinear Refractive Index of ith Wavelength in XPM
ω Anglular Frequency
1
1 Introduction The demand for higher transmission capacity and higher efficiency push optical
communication (OC) to create more complex designs and solutions. In this process, a lot
of various effects occur. Their impact on the transmission depends from particularly
conditions. Optimal setting is a trade-off between introduced distortions due to
phenomena and their relations in the optical fibre and our capabilities to suppress them.
The possibility of pure physical experiments is unacceptable from more points of views.
The response on the current situation is the application of simulation methods as one part
of developing and implementation process. Simulation roughly estimates optimal
parameters and then follows the tuning of physical device(s) or system(s). The simulation
accuracy and therefore success of whole project depends from simulation models and
conditions. At the beginning, credibility of simulation’s outputs should be verified with
basic experiments and then predicts results of desired design.
Second chapter regards the physical phenomena in the optical fibre and within
devices are briefly described. Their relative impact on the total transmission impairments
is evaluated and possibilities of mitigation are considered as well. The events and factors
with positive and also negative consequences on the OC are presumed Current massive
trend in the transmission systems reflects the demand of longer distance and higher bit
rates per channel. Substitution of modulation format has been following as one step to
fulfillment of higher requirements. Primary used on-off keying (OOK) is compared with
differential phase-shift keying (DPSK). Throughout diploma thesis, term DPSK refers to
differential binary PSK sometimes referred to as DBPSK. Properties and applications of
DPSK format consider chapter 3.
PSK detection sensitivity differs from the sensitivity of intensity detection. The
dominant limitation creates phase noise. Its origin results from the finite laser linewidth
and nonlinear phase induced by Kerr effect. The specification of major contributor gives
us system potential. This is the objective of chapter 4, where I want to specify OOK,
DPSK and DQPSK format performance dependents from varying values of amplitude and
phase noise represent by OSNR and laser linewidth for 10 Gb/s and 40 Gb/s. Then,
impact of Kerr effect within NZ-DSF and SMF is evaluated. Assessment will be realized
by simulation software for optical applications “VPI Photonics”, allowing wide range of
WDM and component design.
2
2 Complex approach to optical communication
2.1 Physical characteristic
Today’s optical communication uses transmission medium, that is ultra lossless in
the comparison to other technologies. It offers a bandwidth of 400 nm (equivalent of 54.5
THz), which is defined by loss <0.35 dB/km (see Figure 1) [1]. It is equivalent to 6.8125
billions B channels or 6.8125 millions of TV channels.
Limitations due to losses have got to do three mechanisms:
• Absorption: on the impurities and at IR area (Fig. 1)
• Scattering: predominantly formed by the Raleigh scattering
• Radiating losses: occur at the deep IR area and photonic crystal fibres
» Bending loss: energy emission from the fibre on the turnings, micro and macro
bends at very high wavelengths (Figure 1)
» Seepage loss: energy release through slim cladding, which creates photonic band
gap.
Figure 1: Spectral variation of attenuation; Source [1].
Today’s state of the art fibres are very close to their physical limit and next
enhancement will be able at hollow core fibre based on the band gap photonic crystal
fibre. It has got high losses due to simple manufacturing process. Water content in the
preform and the drawn fibres is too high [2]. Another problem is a manufacturing of the
finesse core surface. Conventional fibres improved over the past 20 years to their current
3
stage. First successful demonstration of hollow core fibre was in 1999 [3]. The question
that arises is how many times do the developers need to overcome processing problems?
2.2 Mitigation of impairments and distortions
Optical pulse is influenced by deterministic and stochastic processes as well during
the whole transmission and which impact the signal features (shape, amplitude and time).
The transfer functions describe deterministic part of the influence. Manufacturing and
also installing processes and their imperfections can be just excesses from calculated
value but they also introduce the stochastic behavior. The source of degradations has got
linear and nonlinear base. Linear processes have an effect on the time domain
characteristics. On other hand, nonlinearities processes influence the spectrum of the
signal and they occur in the case of high power in fibre, which might define more points
of view. Resulting effects have to be evaluated as a compact issue. The level of inevitable
regeneration depends on the working conditions of transmission system, especially on the
number of channels, bit rates and distance.
2.2.1 Nonlinear effects
The response of any dielectric to light becomes nonlinear and intense
electromagnetic fields and optical fibres are no exceptions. On a fundamental level, the
origin of nonlinear response is related to anharmonic motion of bound electrons under the
influence of applied field [4]. Nonlinearities are undesirable during transmission and
have the highest impact at the beginning of amplifier span. They are a limiting factor to
the long distance and high capacity transport systems. The source of nonlinearity is
transmission medium (fibre) and not amplifier [5]. Next, two groups of elastic and
inelastic nonlinear effects, which exist at fibre, will be described.
The simplest way how to cope with nonlinear effects is to prevent them. This can
be achieved via design of new networks, where proper fibre with large effective area can
be applied. Otherwise other methods for specific issue at hand have to be used.
2.2.1.1 Kerr effect
It is elastic in the sense that no energy is exchanged between electromagnetic
field and the dielectric medium. It describes the intensity dependence of the refractive
index. In the simplest form, the refractive index can be written as
2 22( , ) ( ) ( )n E n n Eω ω= + (2.1)
4
The intensity dependence of the refractive index leads to a large number of nonlinear
effects and the two most widely studied are self-phase modulation (SPM), cross-phase
modulation (XPM) and four-wave mixing (FWM) [4].
Figure 2: Products of Kerr effect; [6].
Self-phase modulation
SPM refers to the self-induced phase shift experienced by an optical field during
its propagation. It is responsible for spectral broadening of pulses as a consequence of the
time dependence on nonlinear phase shift ΦNL.
22 0NL n k L Eφ = (2.2)
The time dependence of its time derivation (marked δω) refers to frequency chirping,
Figure 3 a). The Chirp induced by SPM increases in magnitude with the propagated
distance Figure 3 b). The extent of spectral broadening depends on the pulse shape.
5
a) b)
Figure 3: a) Temporal variation of SPM-induced phase shift and frequency chirp for Gaussian
(dashed curve) and super-Gaussian (solid curve) pulse. b) Experimentally observed spectra for a
nearly Gaussian pulse at the output of a 99 m long fibre. Spectra are labeled by maximum phase shift
related linearly to the peak power; [4].
Cross-phase modulation
XPM is always accompanied by SPM when at least two optical frequencies are
propagated simultaneously in the fibre. XPM stands for equally intense optical fields of
different wavelengths the contribution of XPM to the nonlinear phase shift is twice that
SPM. Nonlinear phase shift for the field at ωi is given by
( ) ( )2 0
i iNL i NLn k nφ = Δ (2.3)
22( )
2 2N
iNL i j
j i
n n E E≠
⎡ ⎤Δ = +⎢ ⎥
⎣ ⎦∑ (2.4)
Figure 4: Eye diagram of complete and incomplete collisions; [5].
6
XPM induces timing jitter shown in Figure 4 [5] and it can lead to modulation instability,
asymmetric spectral and temporal changes of copropagating optical pulses [4].
Four wave mixing
FWM transfers energy from strong pump waves to new waves describes
following equations:
4 1 2 3ω ω ω ω= + − (2.5)
4 1 2 3β β β β= + − (2.6)
FWM induces amplitude noise, which is a source of serious degradation shown by Figure
5. However its efficiency is very sensitive on the phase matching [4].
a) b)
Figure 5: a) nonlinear crosstalk due to FWM, b) eye diagram of amplitude noise due to FWM; [5].
Limitations due to Kerr effect have got different nature:
• Interchannel effects: involve phenomena mentioned above and dominate at 10 the
Gb/s channel. These effects have got counterpart at anomalous dispersion regime and
trade-off between both features is strong instrument of how to get optimal conditions
of complex transmission system. Soliton transmission is possible and therefore very
robust pulse over long distance can be achieved. But it has got a lot of issues that have
to be overcome. More modulation techniques are available with the influence on the
final result.
• Intrachannel effects: pulse spreading is high and nonlinear intersymbol interference
becomes the major single-channel penalty, Figure 6. They dominate at 40 Gb/s and
higher bit rate channels [7]. Dispersion induces intrachannel effects, so it is the
limiting factor no more. Different design of dispersion map, which employs fibre
7
spans consisting of three or higher number of concatenated sections is useful. Another
possibility supposes different modulation scheme based on the DPSK format [vsetky
o DPSK]
Figure 6: examples of intrachannel effects; [7].
2.2.1.2 Stimulated scatterings
Optical field transfers part of its energy to the nonlinear medium. Stimulated
Raman scattering (SRS) and stimulated Brillouin scattering (SBS) belong to this group.
They are related to vibrational excitation modes of silica. The main difference is that
optical photons participate in SRS while acoustic photons participate in SBS. In a simple
quantum-mechanical model applicable to both SRS and SBS, a photon of incident field is
annihilated to create a photon at a lower frequency and a photon with the right energy and
momentum to converse the energy and the momentum. Even SRS and SBS are very
similar in their origin, different dispersion relations for acoustic and optical photons lead
to some basic differences.
Stimulated Raman scattering
In any molecular medium, spontaneous Raman scattering can transfer a small
fraction of power (~ 10-6) from one optical field to another, whose frequency is
downshifted by an amount determined by the vibrational modes of the medium. Raman
gain spectrum is specific for the material and for fused silica as shown in Figure 4. This
behavior is caused by amorphous nature of the silica glass and it can be tuned by
dopands.
8
Figure 7: Raman gain coefficient for pure silica and 1550 nm pump wavelength; [8].
SRS occurs when the pump power exceeds a threshold value and then builds up
almost exponentially. The threshold power is explained as follows [4]:
0 16 eff
eff R
AP
L g≅ (2.7)
Typical value of Raman threshold is approximately 500 mW of whole optical power. The
influence of SRS on the WDM system is shown by Figure 5. Impact of SRS is not able to
be reduced by dispersion as not Kerr effect by itself but the dispersion changes result due
to intense presence of Kerr effect [4].
The way to suppress SRS is through power management in optical fibre. First
decision is set the fibre type, mainly its Aeff. Then variation of number of channels and
therefore power level is available. SRS is a challenge and offers next dimension at WDM
design.
Figure 8: The outcome of SRS at WDM system; [5].
9
Stimulated Brillouin scattering
The pump field generates an acoustic wave through the process of
electrostriction. The acoustic wave in turn modulates the refractive index of the medium.
This pump-induced index grating scatters the pump light through Bragg diffraction.
Scattered light is downshifted in frequency due to Doppler shift and propagates in the
backward direction. SBS saturates maximum power per channel in the optical fibre
(Figure 6).
Figure 9: Behavior of input and output power due to SBS; [5].
SBS is a very narrow-band process and its spectral width of gain spectrum is ~ 10 MHz
because it is related to the damping time of acoustic waves. Thus SBS occurs efficiently
for CW pump or pump pulses whose spectral width is smaller than the gain bandwidth.
The threshold power is explained similarly like that of the SRS threshold
0 21 eff
eff B
AP
L g≅ (2.8)
The threshold level predicted by (2.8) is only approximate. The effective Brillouin gain
can be reduced by many factors and therefore SBS can be as low as ~1 mW for a CW
pump and nearly ceases to occur for short pump pulses (width <10 ns) [4].
SBS can be suppressed by dithering laser frequency [5], but is not a limiting
factor of today’s transmission systems.
2.2.2 Amplification
A signal after the passing of specific distance or device has to be amplified on the
required level. Amplifiers set up the real part of device’s transfer function and they are
employed due to compensating losses or setting required power level. Qualitative
characteristics of the amplifier determine the features of transmission system:
10
• Noise figure: describes an inherent process of every amplifier. The noise generated
during amplification has got broadband characteristic and its presence in the signal
band decrease OSNR and transmission capabilities. The noise figure is defined:
IN
OUT
SNRNFSNR
= (2.9)
The maximum number of amplifier spans determines beginning value OSNR, noise
figure of used amplifiers and required OSNR at receiver. Total transmission distance
can be tuned by varying mentioned parameters.
• Bandwidth: is defined by frequencies that belong to 3 dB fall from the peak gain. It
limits the number of channels at WDM system.
• Gain: specifies the level of amplification for the current frequency and therefore
amplifier span or repeater spacing. Longer repeater spans usually mean shorter total
distance due to higher level of ASE. So long haul systems can have a half or less
amplifier span against short haul.
• Gain flatness: it is spectral characteristic of the gain and describes difference of the
lowest and the highest gain from the mean gain. High value induces strong self-
filtering effect, which limits the using of concatenated amplifiers. It will lead to
extremely high dynamic of received signals and drowning of low amplified signals in
the noise. This parameter can be suppressed also after manufacturing by optical gain
flatness filters which can be integrated at amplifier or connected on the amplifier’s
output.
The two amplification’s schemes are suitable to use:
1. Lumped amplification: the amplifiers’ footprint is small comparing to the
transmission size. It is up to 1 km length of fibre. Amplifying is based on the 3 or
4 level model.
2. Distributed amplification: the transmission fibre is also an amplifier
simultaneously. Raman Effect and 3 or 4 levels model is considered as well.
Doped fibre amplifiers
The stimulated emission of the proper quantum jump, which has to be similar to
the transmitted pulses, conducts to the amplification. Rare earth elements are necessary
11
part of structure. It is tuned by appropriate dopants. Today’s knowledge of dopants and
designs reduces their applications on the C, L, O and S band (see Figure 1, Figure 7).
These amplifiers have got high gain and power conversion and the number of
operating windows is sufficient for traffic demand. On the other hand, the minimum level
of noise figure is 3 dB, what can be limit for transoceanic and transcontinental
applications. It influences the length of amplifier’s span. Thus, more amplifiers have to be
deployed with the impact on the cost and reliability. The issue of distributed doped
amplifiers still has been only at theoretical models.
Raman amplifiers
Raman amplifier employs SRS and consists from any transmission fibre and group
of pump lasers lasing on the proper frequencies, which are shifted to upper values to
match maximum Raman gain, 14 THz for silica glass (Figure 8). It can be created by one
laser as well, what depends on the desired parameters. Its operating band is set up by
pump’s wavelength and spectral characteristics are influenced by fibre properties
(dopants and refractive index profile). Raman amplifier is able to amplify whatever band
limited only available laser wavelengths and it is not any barrier.
Figure 10: Characteristic of Erbium amplifier (left) and Raman amplifier (right); [7].
If Raman amplifiers want to reach sufficient gain, they will have to use very high
pump power. Therefore pump efficiency is lower against doped fibre amplifiers moreover
strong Kerr effect occurs with high powers and WDM crosstalk is another issue. On the
other hand they allow to provide negative effective NF in the case of amplification within
the transmission fibre [8].
12
The latest trends in optical amplification have tended to focus on Raman
amplifiers and doped fibre amplifiers are on the edge of interest. Both types have got
unique features, which don’t exclude co-operative realization. Hybrid schemes don’t have
adequate attention. They are able to offer outstanding results (Figure 4) and their potential
should be explored deeper. It will probably happen later, when the requirements on the
transmission will reach higher levels.
Figure 11: Various hybrid amplification schemes; [7].
2.2.3 Shaping
The shape describes modulated envelope applied on the optical carrier. Pulses
used at OC have got finite linewidth and therefore compose from the band of frequencies.
Optical part of spectrum is affected by the dispersion at any material. The dispersion hits
only time domain characteristic of the pulse that assigns individual velocity to every
frequency. It broadens the pulse width during its transmission while the spectrum has
been unaffected It would result to intersymbol interference. It is metaphorically
demonstrated by Figure 5.
13
Figure 12: The dispersion’s influence; [7].
The sequence of frequencies depends from the dispersion regime:
• Anomalous dispersion regime: blue part of pulse goes faster than red part.
• Normal dispersion regime: red part of pulse goes faster than blue part.
The dispersive influence of the optical fibre is called Chromatic dispersion that consists
from two parts:
• Material dispersion: characterizes dispersion properties of the current material.
• Waveguide dispersion: is caused by different refractive index in the core and
cladding due to pulse propagation in the core and also in the cladding, where it has
different velocities. It is variable and permits the tuning by the refractive index
profile. It describes Figure 13.
Figure 13: Material, waveguide and chromatic dispersion for current fibres;
The issue of chromatic dispersion is more important as the bit rates per channel
increase. For a system penalty of 1 dB, the bit rate, dispersion and distance are related as
follows [10]: The dependence of system
2 5 210 / ( / )B DL ps nm Gb s≈ (2.10)
14
It means that four times higher bit rate allows sixteen times smaller tolerance than earlier
value of tolerance. The need of dispersion compensation can accomplish more
technologies:
• Dispersion compensating fibres: use fibre with negative chromatic dispersion joined
after typical fibre and creates part of route. Dispersion is tuned by waveguide
dispersion and modern DCF offer similar value of attenuation and high negative
chromatic dispersion but effective core area is smaller due to refractive index profile.
Recently DCF has overcome other way of dispersion compensation and it is the most
frequent technique.
• Fibre Bragg grating: short piece of fibre up to one meter with concatenated
refractive index pattern, which is designed to refract the incoming frequencies in the
aim to clear their group velocity dispersion. FBG imposes degradation, which can
express NF and it has got high thermal sensitivity and small effective core area [red
book]. It has to use the circulator for proper work.
Figure 14: Dispersion compensation by FBG; [9].
• Optical filters: contain several filter approaches. One of them is already mentioned
FBG, which represents ARMA response and other possibilities is planar waveguide
that meet MA and optical all-pass filter with constant magnitude response. Those
alternatives are used mainly at dispersion equalization [10].
• Soliton transmission: use optical pulses with special shape and power level, where
SPM and dispersion are at equilibrium. Technical issues haven’t allowed commercial
deployment.
Spread pulse
circulator
Chirped FBG
15
Dispersion compensation can perform symmetrical or non symmetrical management. The
first possibility pre-compensates on the inverse value of dispersion maximum. On the
other hand, non symmetrical technique works only at positive interval. On the Figure 10,
there are the results of simulation (left one) and experiment (right one) of symmetrical
and non symmetrical dispersion compensation in the centre (upper row) and in the end
(lower row) of the span [5]. It is clearly seen that symmetrical compensation gives better
conditions for transmission.
......................................... a) b) c) d)
Figure 15: a), c) symmetrical dispersion management; b), d) non symmetrical dispersion
management; [5].
• Dispersion slope: is third member in the Tayler expansion of the propagation
constant. It assigns different value of the dispersion for the various frequencies Figure
11. It introduces next parameter, which characterizes property optical fibre and it has
to be compensated as well. The dispersion compensation doesn’t mean dispersion
slope compensation and it is equalized at the end of the transmission.
Figure 16: The effect of dispersion slope for border and central frequencies; [5].
16
• Polarization mode dispersion: PMD is has got different principle against
phenomena mentioned above. Its stochastic character gives atypical features compare
with previous effects. Whole impact is described by:
» 1st order PMD: wavelength independent, time variant and increases with root of the
length.
» 2nd order PMD: wavelength dependent and occurs after suppression of 1st order
PMD.
The source of PMD is random birefringence along the link and in the components. It
causes various velocities of both parts of linearly polarized mode. Consequently the
pulse spreading occurs (Figure 12). It becomes serious issue from 10 Gb/s and it can
induce temporally high increase of BER. Thus, PMD is important limitation factor at
high speed networks.
Figure 17: PMD due to birefringence effect; [11].
The best way of PMD suppression is to prevent induction of birefringence by the
using of precise technological and installation techniques. Then PMD equalizers can be
employed at the end of link for single channel [4] or low speed polarization-scramblers at
the beginning of the fibre, which should decrease the PMD on the tolerant level [12],
[13]. The last possibility is more efficient than PMD equalizers due to its application on
the whole WDM band.
2.2.4 Jitter
Jitter is stochastic process of every component within transmission system. This
section considers just optical contribution to the jitter. PMD is the strong contributor of
jitter and its origin and suppression was described earlier. Frequency jitter of laser
17
linewidth is transferred to the timing jitter by dispersion of the fibre. Thus, precise and
stable lasers and filters will produce less timing jitter [5]. Another component is
fluctuations of refractive index due to high powers and interaction with dispersion.
Symmetrical dispersion compensation is suitable to remove this effect showed by Figure
13. But this dispersion scheme has to design with amplification scheme and consider
amplifier position due to maintenance of low Kerr effect. Bit-pattern-dependent effects
can remove modulation format with constant power level at every state.
Figure 18: Cancellation of timing jitter with symmetric dispersion profile; [5].
2.3 Modulation format
The information can transmit signal’s amplitude, phase, frequency or combination
of those features. Huge bandwidth offered by optical fibre and high value of laser’s
linewidth have established OOK like gold standard. It offers three variations, NRZ, RZ
and CSRZ, which are more resilient to some effects and also more sensitive to some of
them.
• NRZ OOK: the most tolerant on the chromatic dispersion and optical filtering.
• RZ OOK: the best performance against intra-channel nonlinear effects after
transmission due to the best performance in back-to-back.
• CSRZ OOK: the superior resilience to nonlinearities and represents satisfactory
opinion to meet all key requirements for future all-optical networks [14].
It seems that basic features of the OOK don’t match demands for future all-optical
networks. More precise lasers with narrower linewidth have opened possibilities of phase
shift keying. Today’s situation is suitable for the developing of DPSK transmitters with
18
balanced receiver due to its economical efficiency. DPSK overcomes OOK at following
points:
• 3 dB lower required OSNR for the same BER (theoretically)
• 3 dB lower peak power
• Sensitive on the phase noise
• More resistant against nonlinear effects
• More robust at higher bit rates
2.4 Economical aspects
If we don’t want to do research for research, optimal implementation of every
technology will have to meet following rule, where optical communication (OC) and its
basic, pillar optical technologies (OT), is not an exception:
Solution = ƒ (service)
OC is a part of global market and tries to meet its demand. The predictions of
development are very volatile and whole process of the creating of estimation is difficult.
I specify main factors affects on the OT’s boom and recession.
2.4.1 Catalysts of OT
Traffic growth
Since the year 2000, global traffic has been dominated by internet data. Studies of
traffic of the year 2005 indicated a global traffic growth of 115% per a year. Estimation
of Atlantic traffic through 2025 is illustrated by the Figure 19. Other driving factors
would be globalization of FTTx-xPON access for 10-100-1000 Mb/s BB solutions and
installation and services cost reduction to the current level of xDSL as we are witnesses
nowadays [1].
19
Figure 19: Comparison of IP traffic predictions with installed capacity; [1].
The open issue has been the conditions of IP traffic growth, which stimulates demand for
higher quality multimedia. There will probably be the ultimate limit that average user will
be able to comprehend, but this has yet to be reached [15].
Service convergence and their adaptability to NGN
Sectors of IT and CT have converged to the common platform due to removing of
interworking restrictions and creating open platform environment by the way. This
process has developed with success and disappointment as well. The cheapest alternative
based on IP has been chosen as the basic transport protocol that is not optimal solution for
switching circuit services requiring guaranteed parameters of transmission. Therefore
upgrades to the connection oriented services have to be implemented and they need
approximately up to twice bandwidth compared to legacy systems and adequate margin in
the congestion protection.
Those factors have brought better managing and flexibility of services, unclear
savings and on other hand higher requirement on the capacity of core network.
Introduction of new services
This area includes the roll-out of new services or improving their existing quality.
The main objects of interest are multimedia and real time applications. The latest
demonstration is Triple Play. Its strategy is to offer voice, Internet and video through one
data access. The potential is huge and there will be a lot of modifications.
Dimension of that service is not able to realize without OT. There is also
opportunity for radio and metallic connections but only as final section between customer
and multiplexer.
20
2.4.2 Inhibitors of OT
Providers’ concentration on the short-time objectives
Low-cost solution with fast market returns have become the key driving concerns
of OC innovation. This emphasis prevents industrial and academic research from
exploring technologies that are deemed to immature for short-term deployment and that
have no immediately business value. The phenomenal growth of capacity in recent
wireless BB services has provided a perception that bandwidth is infinite.
But new driving factors to appear in the next 3-7 years, should steer OC industry,
namely: exploding bandwidth demand, lightwave capacity exhaustion and facing ultimate
technology limits [1].
Establishing of the new layer model
One way how to satisfy the demand for higher capacity is revolutionist change of
interconnection’s model and direct mapping from 3rd layer onto physical medium with
new non redundant management either IP or optical layer. This approach represents
IPoWDM and it would replace mapping through ATM and SDH to the WDM layer.
This technique crashes on the deep penetration of the current technology and it
would be alternative solution in the extreme cases.
Technological development at cooperative sectors
OC is a one ring in chain, which brings the service from the server to the
customer’s application. The reliability of service providing determinates the crucial
process as the chain’s strength depends from the weakest ring.
This idea includes negative and also positive development of the similar
technologies. Huge progress on the field of DSP at 1990s meant stop for commercial
deployment of ultra high speed optical systems due to enormous video compression.
Insufficient development of server performance would restrict data traffic and it will
decrease progress of whole ICT sector.
Other reasons
This section should describe phenomena that haven’t got rational base or I haven’t
recognized. One example of my ideas is technological deflation at the end of 20th
Century. It still has been finding the lost goodwill of the investors.
21
3 Differential phase-shift keyed format Phase-shift-keyed (PSK) formats carry the information in the optical phase itself. The
receiver has to compare detected signal with reference signal and extract information.
Due to the lack of an absolute phase reference in direct-detection receivers, the phase of
the preceding bit is used as a relative phase reference for demodulation. This results in
DPSK formats, which carry the information in optical phase changes between bits. DPSK
has got several advantages against ASK modulation thus it is not surprising, that many of
the recent long-haul WDM transmission records at per-channel rates of 10 and 40 Gb/s
are now held by systems based on DPSK.
Optical systems based on DPSK are not new. DPSK was extensively studied in the
late 1980s and early 1990s for use mainly in single-span fiber-optic systems employing
coherent receivers as well as in the context of free-space optical communications, where
the 3-dB sensitivity advantage over OOK could be exploited. When erbium-doped fiber
amplifiers (EDFAs) were introduced, interest in coherent systems declined. For about a
decade, OOK-based WDM systems using optical-amplifier repeaters dominated the
research in long-haul optical communications. Interest in DPSK reemerged several years
ago, as WDM systems were pushed to ever-higher levels of performance [16].
3.1 DPSK format
In the DPSK format, optical power appears in each bit slot, with the binary data
encoded as either a 0 or π optical phase shift between adjacent bits. The optical power in
each bit can occupy the entire bit slot (NRZ-DPSK) or can appear as an optical pulse
(RZ-DPSK). The most obvious benefit of DPSK when compared to OOK is the ~ 3-dB
lower OSNR required to reach a given BER. This can be understood by comparing the
signal constellations for DPSK and OOK, as shown in Figure 20. For the same average
optical power, the symbol distance in DPSK (expressed in terms of the optical field) is
increased by √2. Therefore, only half the average optical power should be needed for
DPSK as compared to OOK to achieve the same symbol distance. This ~ 3 dB benefit of
22
Figure 20: Signal constellation of OOK and DPSK modulation; [16]
DPSK modulation can be only extracted by using balanced detection. In practice, and
neglecting the loss of the optical preamplifier’s input optical isolator, a receiver
sensitivity of 60 photons/bit has been reported for a 10-Gb/s RZ-OOK signal. Using an
RZ-DPSK signal and a balanced-photodiode detection scheme, the sensitivity was
improved to 30 photons/bit. At 42.7 Gb/s, a sensitivity of about 38 photons/bit has been
reported using RZ-DPSK. Again, this is approximately 3 dB better than the best OOK
results of 78 photons/bit. The lower OSNR requirement of DPSK can be used to extend
transmission distance, reduce optical power requirements or relax component
specifications.
DPSK with balanced detection has been demonstrated to offer large tolerance to
signal power fluctuations in the receiver decision circuit because the decision threshold is
independent of the input power. DPSK is more robust to narrow-band optical filtering
than OOK, especially when balanced detection is employed. Numerical simulations and
experiments have shown DPSK to be more resilient than OOK to some nonlinear effects.
This results from the fact that: i) the optical power is more evenly distributed than in
OOK (power is present in every bit slot for DPSK, which reduces bit-pattern-dependent
nonlinear effects) and ii) the optical peak power is 3 dB lower for DPSK than for OOK
for the same average optical power. Finally, an extension to differential quadrature phase-
shift keying (DQPSK) and other multilevel formats should enable higher spectral
efficiency and greater tolerance to chromatic- and polarization-mode dispersion [16].
23
3.2 DPSK transmitter
Two commonly used RZ-DPSK transmitter setups are shown in Figure 21. The
transmitters consist of a continuously oscillating laser followed by one or two external
modulators, typically based on technology. Phase modulation can either be performed by
a straight-line phase modulator [PM, Figure 21 (a)] or by a Mach–Zehnder modulator
[MZM, Figure 21 (b)]. A PM only modulates the phase of the optical field, resulting in
aconstant-envelope optical signal [see measured sampling scope traces in Figure 21 (a)].
Since phase modulation does not occur instantaneously, a PM inevitably introduces chirp
across bit transitions [see symbol diagram in Figure 21 (a)]. A sinusoidally driven second
modulator (“pulse carver”) may be used to carve pulses out of the phase-modulated
signal, thus generating RZ-DPSK. The inset to Figure 21 (a) shows the resulting optical
power waveform. (The seemingly limited extinction ratio of the RZ-DPSK pulses is a
measurement artifact, caused by detecting a 40-Gb/s signal using a 32-GHz-bandwidth
photodiode.)
When using a MZM for phase modulation, the modulator is biased at its
transmission null, and is driven at twice the switching voltage required for OOK
modulation. If a z-cut MZM is used, it is driven in push-pull configuration to minimize
chirp, whereas an x-cut modulator requires only a single electrical drive. Since the phase
of the optical field changes its sign upon transitioning through a minimum in the MZMs
power transmission curve, two neighboring intensity transmission maxima have opposite
optical phase, and a near-perfect 180 phase shift is obtained, independent of the drive
voltage swing. As can be seen from the symbol diagram in Figure 21 (b), the benefit of
highly accurate phase modulation comes at the expense of some residual amplitude
modulation at the transition of two bits, with the width of the resulting intensity dips
depending on the drive signal’s bandwidth and voltage. However, since DPSK encodes
information in the optical phase rather than in the intensity, these dips are of reduced
importance, especially for RZ-DPSK, where the pulse carver cuts out the amplitude-
modulation-free center portions of the bits only, and thus largely eliminates any residual
dips [16].
24
Figure 21: Typical DPSK transmitters: a) implementation with PM, b) implementation with MZM;
[16]
3.2.1 Transmitter evaluation
Transient chirp for PM-based DPSK transmitters and intensity dips for MZM-
based transmitters, the effects of drive waveform imperfections are worth mentioning. The
nonlinear (cosine) transmission curve of the MZM ameliorates the impact of drive-
waveform overshoots or of limited drive-signal rise times. Any remaining imperfections
are only translated into optical intensity variations, but the information-bearing optical
phase is left intact. On the other hand, using a PM for phase modulation, any drive-
waveform imperfections get directly mapped onto the optical phase, thus potentially
degrading performance. Difference of two modulators will arrive, if the driver output
power and the combined driver-plus-modulator bandwidth cannot be chosen arbitrarily
high, which is the case in practice, especially for high-data-rate systems. [16].
3.2.2 Pulse carver
Since DPSK carries information in the phase of the optical signal, optical phase
distortions (such as chirp) will have a severe impact on DPSK receiver performance. At
the transmitter, phase distortions may be caused by imperfect pulse carvers. In order to
operate chirp-free, a dual-drive MZM pulse carver has to have infinite DC extinction, and
25
has to work in perfect push-pull operation, i.e., the sinusoidal drive amplitudes have to be
of the same amplitude and of opposite phase. Any deviation from this ideal condition
inevitably produces chirp. Figure 22 (a) shows three commonly used ways of pulse
carving by applying a sinusoidal drive signal to a MZM-based pulse carver.
Figure 22: a) A typical RZ-DPSK transmitter. (b) Optical intensity and phase waveforms generated
by an imperfect pulse carver; [16].
Three important facts are evident from the optical intensity and phase waveforms
shown in Figure 22 (b): First, when sinusoidally carving at the data rate (50% RZ), the
residual optical phase variations are identical for each bit, while they are different for
adjacent bits when carving at half the data rate (33% and 67% RZ). Since it is the
difference between the optical phase of two adjacent bits that is used to decode DPSK
signals at the receiver, higher degradations due to pulse carver chirp are found for 33%
and 67% duty cycle RZ-DPSK than for 50% RZ-DPSK. Second, we see from the
opposite phase curvatures (50% and 67%) or slope (33%) that chirp due to finite DC
extinction ratios of the MZM can partially be compensated by imbalancing the drive
amplitudes. Third, we notice that for 33% RZ a drive-signal amplitude imbalance leads to
linear phase transitions (i.e., to optical frequency shifts) at pulse center, while a drive-
signal phase error produces a phase offset at pulse center. Since pure bit-alternating
frequency offsets do not disturb the phase difference between adjacent bits at pulse center
(where the intensity is highest, and thus the contribution to the demodulated signal is
largest), a higher tolerance is found for drive amplitude imbalance than for drive phase
errors in the case of 33% RZ. For 67% RZ, the situation is opposite, and we find a higher
26
tolerance to drive phase errors than to drive amplitude imbalance. Experimental as well as
numerical quantifications of pulse carver tolerances for RZ-DPSK can be found in [16].
3.3 DPSK Receiver
A typical balanced DPSK receiver is shown in Figure 23. The optical signal is first
passed through a Mach-Zehnder delay-interferometer (DI), whose differential delay is
equal to the bit period. This optical preprocessing is necessary in direct-detection
receivers to accomplish demodulation, since photodetection is inherently insensitive to
the optical phase; a detector only converts the optical signal power into an electrical
signal. In a direct-detection DPSK receiver, the DI lets two adjacent bits interfere with
each other its output ports. This interference leads to the presence (absence) of power at a
DI output port if two adjacent bits interfere constructively (destructively) with each other.
Thus, the preceding bit in a DPSK-encoded bit stream acts as the phase reference for
demodulating the current bit. Ideally, one of the DI output ports is adjusted for destructive
interference in the absence of phase modulation (“destructive port”), while the other
output port then automatically exhibits constructive interference due to energy
conservation (“constructive port”). For the same reason, the two DI output ports will
carry identical, but logically inverted data streams under DPSK modulation.
Figure 23: DPSK receiver; [16].
27
Careful analysis of the optically demodulated signals at the DI output reveals that the
constructive port carries duobinary modulation, whereas the destructive port carries
alternate-mark inversion (AMI). Today, technical difficulties in implementing stable
delay interferometers have been overcome, and DIs have been demonstrated both in fiber-
based and in planar-lightwave-circuit (PLC) technologies. Fine-tuning of the differential
delay to match the laser center frequency and achieve good interference quality is
typically achieved using a heating element on one of the interferometer arms. Also,
polarization-dependent phase shifts within the DI have to be avoided.
Since both DI outputs ports carry the full (logically conjugated) information, they
can be either detected by themselves (“single-ended detection”), or connected to two
photodiodes using a balanced receiver (see Figure 23). Identical path lengths between the
output coupler of the DI and the point of subtraction within the balanced receiver can be
achieved using variable optical delay units or photonic integration of the detectors with
the DI. Alternatively, separate detection of both output ports in combination with joint
digital signal processing can be applied. The 42.7-Gb/s eye pattern at the output of the
balanced-detector circuit obtained in our experiments is shown in Figure 23 [16].
3.3.1 Balanced versus single-ended detection
Introduction of a detector amplitude imbalance, β, is defined as
A B
A B
S SS S
β −=
+ (3.1)
where SA and SB are the overall opto-electronic conversion factors for the destructive (A)
and constructive (B) DI output ports, respectively. Balanced detection is achieved for
SA=SB, while detection of the constructive (destructive) port alone is found for β=1(β=-1).
Figure 24 (solid curve) shows numerical calculations for the required OSNR at BER = 10-
10 for 33% RZ-DPSK as a function of receiver amplitude imbalance β. It can be seen that
a balanced DPSK receiver performs about 2.7 dB better than its single-ended counterpart.
Also shown (dashed curve) is the required OSNR at BER = 10-10 for OOK, which is (by
definition) independent of β, and comparable to the OSNR needed for single-ended
detection of DPSK. This shows that the frequently cited “3-dB benefit” of DPSK over
OOK, neither is exactly 3 dB, nor is a property of DPSK alone; it is a property of the
modulation format in combination with the detection scheme.
28
Figure 24: numerical calculations for the required OSNR at BER = 10-10 for 33% RZ-DPSK and
OOK as a function of receiver amplitude imbalance β; [16]
Balanced detection in a beat-noise-limited scenario has to be numerically modeled using
the exact probability density functions (PDFs) of detection noise rather than Gaussian
approximations to these PDFs, as is common practice and works well for single-ended
OOK receivers. If Gaussian PDFs are used to represent the noise statistics at the decision
gate, we obtain the dotted curve in Figure 24. While being reasonably accurate for single-
ended DPSK detection, the Gaussian approximation (as well as all simulation techniques
based on the Gaussian noise assumption, such as a standard -factor analysis) is bound to
fail in predicting balanced DPSK receiver performance. The reason for this important
simulation aspect rests in the fact that the tails of the exact (chi-square-like) PDFs differ
significantly from the tails of the Gaussian distributions. For single-ended detection of
DPSK as well as for OOK, this difference in the PDFs, by pure numerical coincidence,
cancels to a high degree of accuracy when calculating BER. In contrast, this beneficial
cancellation is not found for balanced receivers, owing to the different nature of
detection: a single-ended receiver compares a single, noisy signal against a deterministic
(non noisy) threshold to retrieve the digital data, while a balanced receiver essentially
compares two noisy signals against each other [16].
Qualitative physical aspects affected on the detector imbalance include amplitude
imbalance, temporal receiver imbalance, interferometer extinction, delay, phase error,
frequency offsets. Their quantitative impact is shown by Figure 25.
29
Figure 25: Penalties in non ideal RZ-DPSK receivers: (a) Amplitude imbalance in the balanced
detector (dashed curve is for a delay interferometer with an extinction ratio of only 10 dB), (b) Phase
imbalance in the balanced detector, (c) Delay-to-bit rate mismatch in the delay interferometer, (d)
Laser frequency offset from the ideal as set by the interferometer phase difference (dashed curve is
for 33% RZ-DPSK). Circles are experimental results; [16].
3.3.2 Tolerance to Optical Filtering
As mentioned previously, DPSK is more tolerant of tight optical filtering than
OOK. The reason for the good performance can be attributed to the use of ISI-tolerant RZ
coding and higher robustness of balanced DPSK to reduced optical filter bandwidths.
Figure 26: Experimental results of penalties from narrow optical and electrical filtering; [16]
30
Figure 26 shows 40-Gbit/s measurement results for 33% RZ-DPSK. The BER target was
10-9. The gain of balanced DPSK reception over single-ended detection is seen to be some
4 dB, and increases to over 5 dB at low optical bandwidths, where both OOK and the
destructive DI output port show severe penalties [16].
3.4 DPSK transmission at 10 Gb/s
In a linear system employing optical amplifiers, the 3-dB DPSK advantage over
OOK would double the achievable distance by allowing the accumulation of twice as
much amplified-spontaneous-emission (ASE) noise. Limitations from chromatic
dispersion (CD) and polarization-mode dispersion (PMD) are similar for DPSK and OOK
signaling, some chromatic dispersion advantage has been reported for NRZ-DPSK.
However, transmission performance in fiber is also affected by the Kerr nonlinearity. This
is exhibited as four-wave mixing (FWM), self-phase modulation (SPM) and cross-phase
modulation (XPM).The extent of these effects depends on several system design factors,
including average optical power, peak optical power, modulation format, transmission
regime (pulse-preserved or pulse-overlapped), and the nonlinear interaction of signal with
ASE noise.
As in OOK systems, dispersion management can be used in DPSK systems to
reduce the FWM efficiency among WDM channels to low levels. Therefore, interchannel
FWM is generally not a concern. SPM and XPM affect DPSK signals somewhat
differently than OOK signals. In SPM, the intensity variations of an optical signal
modulate the signal’s optical phase via the nonlinear refractive index, causing a red shift
on the rising edges of pulses, and a blue shift on the falling edges. The effect is to broaden
the signal spectrum. The broadened signal spectrum, combined with dispersion, then
broadens the received pulses, introducing a transmission penalty (although we note that
solitons balance SPM and dispersion to maintain pulse shape). For DPSK signals, an
additional effect is important, because the information is carried by the optical phase.
Noise-induced power fluctuations are converted into phase fluctuations by SPM, and
become a source of transmission penalty. This nonlinear interaction of signal and noise is
referred to as the Gordon–Mollenauer effect. In the nonlinear regime, performance
should be substantially different in the two cases for a DPSK signal, while remaining
essentially unchanged for an OOK signal. After nonlinear transmission, the “Q”-factor of
the DPSK signal depended strongly on the transmitter OSNR, whereas the “Q”-factor for
the OOK signal did not.
31
In XPM, the intensity of one signal modulates the phase of another. In OOK systems, the
“collisions” of WDM signals passing through each other impart phase variations that,
when combined with dispersion, result in pattern-dependent timing jitter of the received
pulses. Complete collisions at near-constant power cause less harm, as the phase
variations caused during the first half of the collision are largely undone in the second
half. However, as WDM channels are placed closer together, the difference in
propagation speed between adjacent channels becomes lower, the pulses move through
each other more slowly, and partial collisions increase the XPM penalty. DPSK signals,
however, exhibit power in every bit slot. Therefore, all pulses in a given WDM channel
experience similar collisions, mitigating the XPM effect. Of course, a second-order effect
is expected, as noise-induced amplitude fluctuations on pulses in one channel cause phase
fluctuations in another. Generally speaking, it appears that long-haul 10-Gb/s single-
channel OOK systems can outperform DPSK systems, which are limited by the Gordon-
Mollenauer effect, although we stress that single-channel performance is highly system-
dependent, and that there can be cases in which DPSK will outperform OOK. In 10-Gb/s
WDM systems, both experimental measurements and computer simulations indicate that
DPSK and OOK perform similarly at a spectral efficiency of 0.2 b/s/Hz. At a spectral
efficiency of 0.4 b/s/Hz and higher, DPSK, due to its increased robustness to XPM, can
outperform OOK. However, we again stress that system performance is dependent on
many factors, including channel power and dispersion map [16].
3.5 DPSK transmission at 40 Gb/s
At 40-Gb/s, single-channel effects in the pulse-overlapped (pseudolinear) regime
mainly limit signal transmission. In particular, intrachannel FWM (iFWM) transfers
power between bit slots as pulses disperse into each other and mix due to fiber
nonlinearity. The effect in OOK is amplitude fluctuations on the “1s”, and “ghost pulses”
(residual power) on “0s”. In DPSK systems, the phase fluctuations from this mixing are
more detrimental than amplitude fluctuations. In intra-channel XPM (iXPM), intensity
fluctuations of the dispersed, overlapped pulses modulate the optical phase. The effect in
OOK is timing jitter when combined with dispersion, while in DPSK, both the timing
jitter and the phase fluctuations are detrimental. As mentioned earlier, undistorted DPSK
has 3-dB lower peak power than OOK for a given average power, due to having power in
each bit slot. In the pulse-overlapped regime, nonlinear DPSK penalties can be reduced
because of this more smoothly distributed power. Also, correlation between the nonlinear
32
phase shifts experienced by adjacent bits (due to experiencing a similar environment in
transmission), combined with differential detection and should reduce nonlinear DPSK
penalties. Experimental results have consistently shown better performance for DPSK
than OOK in 40-Gb/s single-channel and WDM systems [16].
3.6 DQPSK application
There have been a number of applications that have been proposed and
demonstrated for PSK. One of these is to increase spectral efficiency through the use of
multilevel signaling. In particular, DQPSK has recently received intense study. The most
widely used implementation of a DQPSK transmitter and receiver is shown in Figure 27.
The transmitter consists of two parallel DPSK modulators that are integrated together in
order to achieve phase stability (a serial arrangement is also possible, and has been used
Figure 27: DQPSK transmitter and receiver; [16].
in experimental demonstrations). The receiver essentially consists of two DPSK receivers,
although the phase difference in the arms of the delay interferometers is now set to +π/4
and -π/4. The benefit of DQPSK is that, for the same data rate, the symbol rate is reduced
by a factor of two. Consequently, the spectral occupancy is reduced, the transmitter and
receiver bandwidth requirements are reduced, and the chromatic dispersion and PMD
limitations are extended. As compared to DPSK, the required OSNR to reach a given
BER is increased by about 1–2 dB, depending on the BER. Also, the frequency offset
tolerance between the laser and the delay interferometer is about six times less than for
DPSK, making the DI design and stabilization somewhat challenging. Even higher
spectral efficiency can be achieved using various combinations of phase- and amplitude-
shift keying. Such multilevel modulation can also improve system tolerance to chromatic
33
dispersion and PMD. However, these schemes quickly become quite complicated to
implement, require higher OSNR, and are sensitive to nonlinear phase noise [16].
34
4 Trends in the optical communication Development of OT has got good drive although it doesn’t reach its maximum from
the last decade of 20th Century. History, the newest requires and economical background
have formed design of OC. One clearly defined direction is price cut and rising bit rates
per channel up to 40 Gb/s. Those hints can realize more ways and their short description
follows.
4.1 Transmission bands and spectral efficiency
The choice of transmission band is not very difficult. Physical properties of existing
infrastructure and compensation technique lead to the C and L band exploitation. They
are feasible in the case of required capacity, availability and reliability. Higher
requirements can handle two alternatives that represent the using of another band or
improving spectral efficiency. Second variant has applied till now. It includes narrower
channel spacing and multilevel modulation. Its potential is finite and occupying of next
band will come sooner or later.
4.2 Multiplexing techniques
The growing demand for higher bit rates can accommodate two different
multiplexing techniques, which have got different approaches of the exploitation of
offered bandwidth. Another fact is enhanced characteristics of available sources including
narrower linewidth.
4.2.1 Time division multiplex (OTDM)
OTDM is serial transmission of number time delayed channels with lower bit rates
to the common channel at one wavelength. Key parameters are at time domain. Its huge
bandwidth is very sensitive on the value of total dispersion and timing jitter. This one
channel hasn’t got enough power to induce nonlinear effects. OTDM allows dynamic
allocation of offering transmission capacity, BoD service. Then, it supports QoS and
optical burst switching (OBS) and optical packet switching (OPS) are supposed but every
device has to work at one data format and their number may be high.
35
Optimal deployment of OTDM is metropolitan and access networks, where bit
rate flexibility is required.
Four times higher speed WDM requires four times higher number of link
terminated devices against the same number of link terminated devices at OTDM. On the
other hand, OTDM requires precise dispersion management with low PMD and higher
OSNR. The transmission capacity of OTDM reaches only fragment of DWDM
performance due to maximum frequency values and lack of capabilities for processing in
optical domain. The parameters of the state of the art electronics is shown by Table 1
[17]. HEMT HBT
GaAs InP SiGe InP
Mux/Demux Gb/s 45 1441 1322 1203
Driver @ 40G VPP 8 - 5 124
1 Fujitsu, 2 IBM, 3 NTT, 4 Lucent
Table 1: Parameters of ultra high speed electronics; [17]
OTDM hasn’t reached required feasibility and the metro and access networks use
others technological solutions.
4.2.2 Wavelength Division Multiplex
WDM is parallel transmission of number of channels within one fibre. The key
parameters are at spectral domain. Thus, nonlinear effects and linewidth of sources are
cardinal issues. The chromatic dispersion and PMD become crucial at long haul systems.
Basically, it is circuit switching technique, which forms its characteristics such as higher
employed bandwidth of the fibre, the channel independence, data format transparency.
The optimal application for WDM deployment is at core and backbone networks.
4.3 Simulation
4.3.1 DQPSK format
BER curve of PSK modulation describes Figure 30 a). There are experimental
results of DQPSK format [18], and the object of investigation was impact of various
values of OSNR and laser linewidth on the narrowband filtered DQPSK modulation in
36
the back-to-back configuration. It represents BER of the transmitter. I have used it as
verification of my simulation model. Its experimental setup is shown by Figure 28.
Figure 28: Experimental setup of; [18].
I created equivalent setup to its scheme and it is shown by Figure 29. I used
generator of additive white Gaussian noise (AWGN) instead of optical amplifier.
Figure 29: Simulation scheme of BER = ƒ (OSNR).
NRZ-DQPSK source consists from CW laser followed by two dual stage Mach-
Zehnder modulators. The used bit rate was 10 Gb/s. The source output power and power
density of AWGN was set on the values, that corresponded to OSNR = 5 dB. Attenuator
modified level of OSNR in the range from 5 to 20 dB. Signal passed through 1. order
Gaussian bandpass filter with 6 GHz linewidth (spectral efficiency equals to 1.67 b/s/Hz),
what was identical with experiment. Signal was demodulated in the optical delay line
demodulator and detected at balanced receiver. At the end, BER was assigned to every
value of OSNR. It was done for 0, 10, 20, 50 and 100 MHz laser linewidth. The
simulation results are shown by Figure 30 b).
37
a) b)
Figure 30: Comparison of experimental [18] and simulation output.
Maximum deviation was in the range of one order, what gave sufficient
likelihood. Next step involved increasing of bit rate on the 40 Gb/s and filter bandwidth
expansion on the equal value of spectral efficiency. The verification was based on the two
assumptions:
1. theoretical prediction that the same BER value for 40 Gb/s transmission requires 6
dB higher OSNR level compared to 10 Gb/s transmission due to noise power
2. application of previous prediction and obtained results from first simulation.
The results for 10 and 40 Gb/s are shown by Figure 31.
38
Figure 31: BER vs OSNR for 10 Gb/s and 40 Gb/s DQPSK format.
The previously mentioned assumptions were not accomplished completely. Only
ideal source met prediction completely. Other curves haven’t got typical inflexed point
and don’t converge to typical value for current phase noise (corresponds to linewidth). It
is partially satisfied approximately until 15 dB or BER = 10-4. The variant with 40 Gb/s
bit rate was not estimated with desired likelihood. The reason of that act may be various.
One possibility could be small time window and only small part of frequencies had been
generated and processed in the BER estimator. Another variant comprises problem(s) at
simulation model. Incorrect conditions, impertinent algorithm or mistake in the algorithm,
which can skip noise at calculation, because proper dependence occurs in the convex part
of curve (until 15 dB) and the absence of inflexed point concave part of curve. The first
one couldn’t be tested due to lack of available memory. Second one is the good question
to designers of software.
Finally, the 40 Gb/s case hasn’t been considered.
4.3.2 DPSK format
Another simulation investigated DPSK modulation. The setup was modified by
DPSK components. DPSK source consisted from CW laser and one dual stage Mach-
39
Zehnder modulator. Laser power was set on one half of the previous value. Filter has got
double bandwidth due to the same spectral efficiency. One delay line interferometer with
single balanced receiver was employed and BER estimation provided the same module.
The scheme shows Figure 32.
Figure 32: Simulation scheme of BER = ƒ (OSNR).
I haven’t got experimental data from DPSK measurements. Thus I used theoretical
predictions and previously verified DQPSK simulation. DPSK should have identical
behavior like DQPSK (shape of BER curve). Two signal’s states of DPSK against four
signal’s states of DQPSK are able to reach the same BER level at worse conditions,
because the linewidth has to be much lower than modulation bandwidth.
The transmission bit rate was 10 Gb/s. The output data corresponds to theoretical
predictions that DPSK is more resistant against phase noise. The divergence of
particularly curves is not rapid, but typical flat waveform occurs for 1 GHz linewidth. The
OSNR difference between DQPSK and DPSK shows better performance of DPSK. Its
benefit increases with lower BER. Identical trends but different setup is reported too [18].
40
Figure 33: BER vs OSNR for 10 Gbs and 40 Gb/s DPSK format.
The DPSK source generated 40 Gb/s stream didn’t repeat the specific behavior of
coherent systems with phase noise. The Flat waveform is missing but convex part is
assessed very well, but only one curve with inflexed point and it fused with others. This
case excludes possibility of low value of time window, because source with 1 GHz
linewidth was described correctly at 10 Gb/s bit rate. It indicates problem at simulation
model.
The simulation variant 40 Gb/s DPSK will not be joined at next considerations.
4.3.3 OOK format
The simulation of OOK format didn’t give reasonable BER values. It has
displayed the same number for different values of OSNR. So, OOK is not evaluated.
4.4 Impact of Kerr effect
4.4.1 Description of simulation scheme
Kerr effect occurs in the presence of high power. Its influence is significant until
effective fibre length. Therefore my scheme is adapted on the investigation of Kerr effect
(Figure 34). Four channels WDM system was set to catch the FWM influence. This
41
simulation is the extension of previously investigated DPSK, DQPSK and OOK formats.
It will comprise the BER of transmitter affected by Kerr effect within part of fibre span.
Then, the resilient of current format can be derived.
The main part of parameters is identical with previous simulations. Channel
spacing is set on the 50 GHz. The optical fibre is arranged in the 4 km long fibre loop.
DCF is insert between transmission fibre and measurement devices. Demultiplexing
provides the identical filter like in the previous case. Optical pulse passes five times
through a loop and after every circle is created set of measurements. It includes optical
spectrum, eye diagrams of signal’s channels and power levels of selected signal channel
and two lower, two upper induced bands. Simulation set comprises two common types of
optical fibres (SMF, NZ-DSF), three modulation formats examined previously and two
various sources. First one demonstrates common telecommunication (DFB) laser type
with 2 MHz linewidth and second one represents today’s high-end (DFB) laser but
ordinary one after certain time (it is hard deal to specify that time, I guess until two years)
with 500 kHz linewidth. Better DFB lasers are available as well.
Figure 34: Simulation scheme of FWM generation.
Computing resources were not adequate to software requirements. It led to the
crashes of whole simulation. Lower global parameters had to be used and consequently
BER estimation is not available. Therefore quality assessment has to use only eye
diagrams, which don’t reflect real affects on the BER. On the pictures, there will be cases
that deploy NZ-DSF, what means worse alternative.
42
4.4.2 OOK performance
OOK should be the less resilient format and simulation confirmed it. Bit-pattern-
dependence introduced the highest amount of amplitude noise to eye diagram. Narrower
linewidth has no effect on the performance; see Figure 35, Figure 36.
a) b)
Figure 35: Eye diagram of OOK transmitter, a) 2 MHz linewidth, b) 500 kHz linewidth
43
Figure 36: Eye diagram after first loop.
Figure 37: Spectrum after first loop.
44
4.4.3 DPSK performance
This format is more sensitive on the laser linewidth, Figure 38. On the other
Figures, there are dependences with 500 kHz linewidth. The eye diagrams (Figure 39) are
smoother than OOK ones. Signal’s bands in the spectrum have got approximately the
same amplitude for OOK and DPSK as well. The nearest noise bands are higher for
DPSK (Figure 40) compared to OOK spectrum (Figure 37) but on the other hand, other
FWM products have to be higher in the OOK spectrum, due to energy conservation. The
eye diagrams opening are approximately identical, but in the back-to-back condition
OOK has got advantage of ~2.5 mW higher contrast (difference between low and high
level). It means that DPSK is more resilient than OOK.
a) b)
Figure 38: DPSK back-to-back eye diagram of a) 2 MHz and b) 500 kHz linewidth
45
Figure 39: DPSK eye diagram after the first loop.
46
Figure 40: DPSK spectrum after the first loop.
4.4.4 DQPSK performance
Investigation of modulated DQPSK format suffers bit interference at symbol. The
distortion assessment on the DQPSK may bring the focusing on the bottom curve in the
eye diagram (Figure 42). It shows similar distortion as DPSK (Figure 39). Certainly the
final impairment is more serious than DPSK case and it has to consider also fidelity of
demodulation. The FWM products generation (Figure 43) has got similar behavior
compared to OOK format (Figure 37).
47
Figure 41: DQPSK eye diagrams in the back-to-back condition a) 2 MHz, b) 500 kHz.
Figure 42: DQPSK eye diagram after the first loop.
48
Figure 43: DQPSK spectrum after the first loop
4.4.5 Potential of best setup
DPSK format deployed 500 kHz laser linewidth reached the best performance, which
can be enhanced by using new type of optical fibre with large effective area and sources
with even narrower linewidth. Following Figures (44-46) show the best results of my
simulation.
49
Figure 44: DPSK eye diagram after first loop
Figure 45: DPSK spectrum after firrst loop
50
Figure 46: Signal power of selected channels relate on the number of loop
51
5 Conclusion My diploma thesis reflected limiting factors of today’s optical communication
systems emerged from relevant physical phenomena in the optical fibre and optical
devices with possibilities of their suppression as well. The domination of positive mood
followed from economical aspects. Consequently, proposed trends in the optical
communication involved wide spectrum of issues and their answers will be given by
particularly situation. DPSK format, basic component of outstanding solutions, was
described with its properties and applications.
Performance of DPSK and DQPSK transmitters was examined for various values of
OSNR and laser linewidth for today’s 10 Gb/s and future 40 Gb/s gold standard bit rates.
Model deployed higher bit rate is not absolutely relevant, because it doesn’t contain
inflexed point and concave part of characteristic BER curve. It was probably caused by
settings or nature of simulation algorithms. Model of lower bit rate estimation has worked
reliably and it was used for the evaluation of Kerr effect on the DPSK and OOK
modulation formats for two types of optical fibre and two laser linewitdhs. This influence
hasn’t been simulated due to high software requirements on the memory. Then, only
qualitative analyze was realized from eye diagram opening.
Modulation formats were evaluated within four channel’s WDM system, where
DPSK format was more resistant against Kerr effect than OOK. The nature of spectrum
FWM products is narrower with high levels at next adjacent noise channels compared
with OOK, which noise products affects wider spectrum. Binary DPSK modulation
outperforms DQPSK and not only in the case of wider laser linewidths but also required
difference of OSNR for the same BER rises with increasing BER value.
The models used in this diploma thesis evaluated impact of transmission channel on
the three modulation types of optical signal. It is good preparation to complex assessment
of particularly component limitation contribution to whole BER value.
Higher computing force will be needed to get better results and collaboration with
VPIsupport seems to be essential on the road to the successful results of simulations.
References:
[1] E. Desurvire, Optical Communiations in 2025, Glasgow: ECOC 2005
[2] Crystal Fibre: the fibre of the future?, Opto & Laser Europe, IOP Publishing
Limited, Bristol, UK, December, 2001
[3] Photonic fibre finds its first applications, Opto & Laser Europe, IOP Publishing
Limited, Bristol, UK, April, 2004
[4] G. P. Agrawal: Nonlinear Fiber Optics Third Edition, London, Academic Press,
2001.
[5] A. Mecozzi, Modeling of high-data rate optical communication systems:
propagation, detection and noise, Glasgow: Short Course6 - ECOC 2005
[6] A. K. Dutta, N. K. Dutta, M. Fujiwara: WDM Technologies: Optical networks,
London, Elsevier Acadmic Press, 2004.
[7] S. Bigo, Optimizing terrestrial systems for 40 Gbit/s channel bit rates, Glasgow:
ECOC 2005
[8] VPIcomponentMakerTM, Optical Amplifier User’s Manual, Berlin, Germany,
VPIphotonics, 2005,
[9] https://vzdelavanie.utc.sk/moodle/mod/resource/view.php?id=4621
[10] Ch. K. Madsen, J. H. Zhao: Optical filter design and analysis A signal processing
approach, Toronto, Canada, John Wiley & Sons, Inc., 1999
[11] https://vzdelavanie.utc.sk/moodle/mod/resource/view.php?id=1162
[12] N. Yoshikane, I. Morita, 1.14 b/s/Hz Spectrally Efficient 50 85.4-Gb/s Transmission
Over 300 km Using Copolarized RZ-DQPSK Signals, Journal of Lightwave
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Mardoyan, A. Konczykowska, F. Jorge, S. Bigo, WDM Transmission at 6-Tbit/s
Capacity Over Transatlantic Distance, Using 42.7- Gb/s Differential Phase-Shift
Keying Without Pulse Carver, Journal of Lightwave Technology, Volume 23, Issue
1, January, 2005
[14] E. Pincemin, Y. Guilloux, A. Bezard, T. Vargas, Robustness of the OOK
Modulation Formats at 40 Gbit/s in the Practical System Infrastructure, Glasgow:
ECOC 2005
[15] VPItransmissionMakerTMWDM, User’s manual, Berlin, Germany, VPIphotonics,
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[16] A. H. Gnauck, P. J. Winzer, Optical PSK transmission, Journal of Lightwave
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[17] R. Ludwig, Ultrafast Transmission Technology, Glasgow: ECOC 2005
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3, March, 2006
Statutory declaration
ČESTNÉ VYHLÁSENIE
Vyhlasujem, že som zadanú diplomovú prácu vypracoval samostatne, pod
odborným vedením vedúceho diplomovej práce Ing. Jozefa Dubovana a používal som len
literatúru uvedenú v práci.
Súhlasím so zapožičiavaním diplomovej práce.
V Žiline dňa .............................. podpis diplomanta..............................
Acknowledgment
POĎAKOVANIE
Touto cestou sa chcem poďakovať všetkým, ktorí sa akýmkoľvek spôsobom
podieľali na realizácii tejto diplomovej práce. Špeciálne by som sa chcel poďakovať
najmä, Ing. Jozefovi Dubovanovi, Prof. Ing. Milanovi Dadovi, PhD. a Ing. Miroslavovi
Bystrianskemu ktorí mi venovali svoj čas a energiu. Navyše rodine a blízkym ďakujem za
vytvorenie vhodných podmienok nielen počas tvorbe tejto práce, ale celého štúdia a ich
podporu v ťažkých obdobiach.
Autor