ece 4670 spring 2014 lab 3 mixers and amplitude...

ECE 4670 Spring 2014 Lab 3Mixers and Amplitude Modulation

1 IntroductionThe underlying theme of this lab is amplitude modulation. Considerable up-front effort will beplaced on the exploration of circuits that perform signal multiplication. Signal multiplication ofbaseband signals and radio frequency (RF) signals is quite challenging. In the co-requisite lecturecourse you have likely already been introduced to linear modulation. This lab will explore basiclinear modulation and demodulation using the envelope detector.

1.1 Background1.1.1 Linear Modulation

Signal multiplication is fundamental to the generation of linear modulation. Recall that in doublesideband (DSB) modulation, the transmitted carrier xc.t/ is created from message signal m.t/ via

xc.t/ D m.t/ Ac cos.2fct C / (1)

where Ac is the carrier amplitude and fc is the carrier frequency in Hz. For the special case of asinusoidal message m.t/ D Am cos.2fmt /, we have that

xc.t/ D Am cos.2fmt / Ac cos.2fct C /

DAmAc

2

cos.2.fc fm/t C /C cos.2.fc C fm/t C /

(2)

1.1.2 Frequency Mixers

If it existed, an ideal multiplier would perform the function

y.t/ D x1.t/ x2.t/ (3)

as shown in Figure 1. A circuit that comes close to being an analog multiplier is the Texas Instru-ments MPY-634, shown in Figure 2. This part has limited bandwidth and is rather expensive. Inpractice, however we have to accept approximations that are available via various analog circuitdesigns. In the world of RF circuit design the term mixer is more appropriate, as an ideal multi-plier is rarely available. Instead, active and passive circuits that approximate signal multiplicationare utilized. The notion of mixing comes about from passing the sum of two signals through anonlinearity, e.g.,

y.t/ D Œa1x1.t/C a2x2.t/2C linear + other higher-order terms

D a21x

21.t/C 2a1a2x1.t/x2.t/C a

22x

22.t/ (4)

In this mixing application we are most interested in the center term

ydesired.t/ D 2a1a2

x1.t/ x2.t/

(5)

1.1 Background

y t

x2 t

x1 t

Figure 1: Ideal multiplier block diagram.

V-IX1

X2

Y1

Y2

Z1

Z2

V-I

V-I

SF

MultiplierCore

VoltageReferenceand Bias

0.75 Atten

A VOUT

–VS

+VS

(X1 – X2)(Y1 – Y2)SFVOUT = A – (Z1 – Z2)

Transfer Function

PrecisionOutput

Op Amp

FEATURES! WIDE BANDWIDTH: 10MHz typ! ±0.5% MAX FOUR-QUADRANT

ACCURACY! INTERNAL WIDE-BANDWIDTH OP AMP! EASY TO USE! LOW COST

APPLICATIONS! PRECISION ANALOG SIGNAL

PROCESSING! MODULATION AND DEMODULATION! VOLTAGE-CONTROLLED AMPLIFIERS! VIDEO SIGNAL PROCESSING! VOLTAGE-CONTROLLED FILTERS ANDOSCILLATORS

TI MPY634

Figure 2: The MPY-634 analog IC multiplier.

Clearly this mixer produces unwanted terms (first and third), and in general may other terms, sincethe nonlinearity will have more than just a square-law input/output characteristic. A diode oractive device can be used to form mixing products, and in particular we consider a dual-gate MEtalSemiconductor FET (MESFET) mixer as shown in Figure 3.

The double-balanced mixer (DBM), which can be constructed using a diode ring, providesbetter isolation between the RF, LO, and IF ports. When properly balanced the DBM also allowseven harmonics to be suppressed in the mixing operation. A basic transformer coupled DBM,employing a diode ring, is shown in Figure 4 along with an active device implementation. TheDBM is suitable for use as a phase detector in phase-locked loop applications too. In this lab youwill using a diode-ring based DBM from MiniCircuits.

A general model for the RF output frequencies of a DBM driven with sinusoidal inputs, say atfIF and fLO, is that the output will contain frequency components at:

fRF D nfIF; nfLO; and jnfIF ˙mfLOj; n;m D 1; 2; : : : (6)

This quite a mess of frequency terms. The balanced nature of the mixer means that the nfLO terms

ECE 4670 Lab 3 2

1.1 Background

+5V

R2

C4

L3

47pF

L4

C8C7Q1NE25139

IF270nH270nH

82pF

C3

42pF

0.01uF

10Ω

C8R1 C5

47pF0.01uF

270Ω

L15 turns, 28 AWG.050 I.D.

C10.5pFLO

5 turns, 28 AWG.050 I.D.

C2

L2

0.5pF

RF

G1

G2D

S

Dual-Gate MESFET Active Mixer

VRF

VOUT

VIN

VLO

zL

Nonlinear Device

Mixer concept

Figure 3: Nonlinear device mixer: (a) Concept, (b) Device implementation.

tend to be suppressed, but the square-wave nature of the LO signal found in a DBM means that theodd harmonics are still noticeable. The drive or amplitude level of the LO is generally required tobe the largest signal present in the DBM.

In this lab you will be exposed to a traditional passive DBM, like that of 4. Since DBM’s oper-ate at radio frequencies (RF) the circuit design requires proper impedance matching to achieve thebest performance. The next subsection describes some of the interfacing circuit design considera-tions.

1.1.3 RF Interfacing Circuits

When working with radio frequency (RF) circuits, extra care is needed to avoid loss of signalintegrity. The SRA-3A+ DBM is an RF circuit designed to operate in a 50 ohm impedance envi-ronment. This means that as we interface to and from this circuit we do so trying to minimize leadlengths and trying to maintain 50 ohm source and load impedances if at all possible. Lack of careresults in extra signal leakage between device ports.

To minimize port interactions one approach is to pad interfaces when say two mixers are con-nected together. A pad is a resistive or lossy attenuator circuit, that maintains Z0 level impedancematching at both ports. The schematic for a T-pad and a Pi-pad is shown in Figure 8. The design

ECE 4670 Lab 3 3

1.1 Background

02 91 81 71

DNG

+FI

-FI

DNG

61DNG

13

12

11

14

15

GND

GND

GND

LO2LO2

LO1LO1

4

3

2

1

RFBIAS

TAP

RFRFIN

5GND

LO SELECT

GND

6 7 8 9

VCC VCCD NG

D NG

LE SOL

01

MAX9982

IF OUT

4:1 (200:50)TRANSFORMER

41

25V

3C9

C10

C7

C6

C11C8

R3L1

R4L2

T1 6

5V5V

C5C4

R1

C2

C1

C3

825 MHz to 915 MHz SiGe High-Linearity Active DBM

vo(t)

mixer

D3 D4

D1D2inputLO

R G

LO source

vp(t)

inputRF

R G

RF source

R L

IF load

vi (t)

IFout

Passive Double-Balanced Mixer (DBM)

Figure 4: The double-balanced mixer: (a) Diode ring with transformers, (b) Active high linearityDBM.

ECE 4670 Lab 3 4

1.1 Background

Pin ConnectionsLO 8

RF 1

IF 3,4^

GROUND 2,5,6,7

CASE GROUND 2^ pins must be connected together externally

Outline Drawing

Schematic

(IF)

(RF)(LO)

Figure 5: MiniCircuits SRA-3+ DBM summary features.

DBMX2

PortRFNum=2

PortIFNum=3

PortLONum=1

TF3TF2

T2=1.00T1=1.00

1

2

3

3

1-T1

1-T2

1

TF3TF1

T2=1.00T1=1.00

1

2

3

3

1-T1

1-T2

1

ap_dio_1N4148_1_19930601D3

ap_dio_1N4148_1_19930601D4

ap_dio_1N4148_1_19930601D2

ap_dio_1N4148_1_19930601D1

LO RF

IF

LORF

IF

Top Level Pushed into hierarchy

Figure 6: Idealized DBM used in ADS to model mixing characteristics: (left) top-level, (right)pushed into the detail level of the schematic.

equations for these circuits are simple, we want to maintain a Z0 impedance level, typically 50ohms, and we want a particular attenuation in dB, say AdB. For the T-pad the design equations are

R1 D Z0

pN 1pN C 1

(7)

R2 D 2Z0

pN

N 1(8)

where N D 10AdB=10. For the Pi-pad the equations are

R1 D Z0

pN C 1pN 1

(9)

R2 DZ0.N 1/

2pN

(10)

In this lab it is suggested that you use the T-pad design when a Pad is needed.

ECE 4670 Lab 3 5

1.2 Laboratory Exercises

RFGND

LO

GND

IF

100 nf inseries onIF line

Figure 7: Breakout board containing the SRA-3.

!!!!

!"

T-type attenuator (pad) Pi-type attenuator (pad)

!"

!! !!

Figure 8: T-pad and Pi-pad resistive attenuator circuits.

At time an RF signal must be split into two paths for driving multiple devices. One suchmeans for doing this, and maintaining an impedance match is a resistive power splitter/combiner.SInce resistors are used to maintain an impedance match signal loss is involved. The loss helpsprovide some isolation between the ports and hence helps reduce signal leakage. Figure 9 givesthe schematic and design equation for a 6dB resistive power splitter. When Z0 D 50 ohms, thismeans that R D 50=3 D 16:67 ohms. The closest stocked resistor value is 18 ohms.

1.2 Laboratory Exercises1. To become familiar with the characteristics of a practical mixer apply sinusoids to the LO

and IF inputs as shown in Figure 10. As a matter of practice one input is always a large signaland the other is always a small signal, in amplitude that is. Here make the LO signal be 1vpeak into 50 ohms at a frequency of 1 MHz. Set the IF put to 100 kHz with a 200 mv peakamplitude. Observe the RF port output on the spectrum analyzer with a 50 ohm termination.

ECE 4670 Lab 3 6


!! "

!! "

!! "!"#$%&

!"#$%'

!"#$%(

)*#*%!+%,%-+%"./0

Figure 9: Resistive power splitter/combiner which introduces 6 dB loss.

Agilent 33120A

Output

1.00000 MHz

Agilent 33120

SRA-3+IF

LO

RF To 50 ohm porton spectrum analyzer200mv pp

2v pp1 MHz

Agilent 33250A

Output

50.000 kHz

Agilent 33250

50 kHz

Figure 10: Basic DBM test circuit.

Observe the output spectrum from 0 Hz up to 5 MHz and catalog the frequencies within 60dB of the strongest signal. Categorize the signals into the three types of mixing products of(6).

2. Compare your measured results with results produced by the idealized DBM model in theADS circuit of Figure 11. Sample output results are shown in Figure 12. You will need todownload a ZIP package from the Web Site. Note the amplitude levels in the ADS model ofFigure 11 are peak values, but the effective output voltage when driving a source matchedload becomes one half this, e.g. 200 mv peak at a generator becomes 100 mv peak = 200 mvpp across the load or input port of the mixer.

3. With the basic characterization complete, you will now build a DSB modulator cascadedwith a demodulator, using a coherent carrier in the demodulator. The circuit schematic isshown in Figure 13. Configure this circuit using the RF interface elements described inthe background section. Observe on the spectrum analyzer that the original message signalappears at the output (IF port) of the second mixer. How important is it that the demodulationcarrier source be phase coherent with the transmitted carrier source?

4. Observe the output waveform on the scope to verify that among the various signal compo-nents that are now super imposed, the desired message signal is indeed present. How can werecover the message signal?

ECE 4670 Lab 3 7


!"#$%

&'()*+,-.&'()*+,-./&'()*+,-./0('()*"%,-.1!"#$%23425"&,#6)/78294:;<2944=

>

&'()*+,-.

!%?8.)?@A/

B,)C0943:;<DE(F8%$G)047H3!!G*043!

+,-.+,-./

I-J+8E)?%)(09743.')*?%#(+8E)0H44743$')*

+@DK?5LK+

!%?8.)?@AH

B,)C0/3I;<DE(F8%$G)0/3!!G*043!

@@M@0943NOE

PQIR/

@@/@0943NOE

@@H@0943NOE

5"&,#6)5"&,#6)/

Figure 11: ADS DBM basic test circuit.

!"# $"! $"# %"! %"# &"! &"# '"! '"#!"! #"!

()!

(*!

('!

(%!

!

($!!

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+,-./-012345678

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$"!#!567

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%"!!!N*

Figure 12: ADS DBM basic test circuit RF output spectrum.

5. Attempt to recover the message signal, the 50 kHz sinusoid, using a simple RC lowpassfilter. Capture the time domain results in the scope. Make note of any strong interferencesignals that you see via the spectrum analyzer.

6. Compare your results with the ADS simulation of Figure 14 and ADS results similar tothose shown in Figure 15. You will need to add a model for your RC lowpass filter into the

ECE 4670 Lab 3 8


Agilent 33250A

Output

50.000 kHz

Agilent 33120A

Output

1.00000 MHz

SRA-3+IF

LO

RF

To 50 ohm porton spectrum

6 dBPowerSplitter

6 dBPad

SRA-3+

Agilent 33250

Agilent 33120

LO

RF IF

200mv pp

2v pp1 or 2 MHz

55 – 50 KHz

analyzer

Figure 13: DSB modulator followed by a coherent demodulator.

simulation.

!"#$%

!%&'()&*+,

-.)/0,123456789'%$:)01;<2!!:=012!

!%&'()&*+<

-.)/0,2>456789'%$:)0<2!!:=012!

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**N*0I12JK7

AE>O<

?C8)=G.@(?C8)=G.@(,?C8)=G.@(,08C8)="%.@(P!"#$%Q21QL"?.#M),;'Q,1345QI11R

S

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**,*0I12JK7

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>@VG'7)&%)80I;12(C)=&%#8G'7)0<11;12$C)=

G*6F&LWFG

**U*0I12JK7

AE>O,

Figure 14: ADS DSB modulator/demodulator circuit.

7. AM modulation can be demodulated using envelope detection. This simplicity is the basisfor AM radio broadcasting over carrier frequencies from 540 kHz to 1600 kHz. Here youwill generate an AM modulated carrier at 1 MHz using the built-in modulation capability ofthe Agilent 33250. The circuit schematic is shown in Figure 16.

8. Configure the Agilent 33250 to generate a 1 MHz AM carrier with a message signal initiallyat 10 kHz and a modulation index of 75%. You may need to refer to the Agilent 33250to learn how configure the generator for AM modulation.The generator need to drive anenvelope detector which consists of a 1N4148 silicon diode followed by an RC filteringcircuit. Note that this is a nonlinear circuit.

ECE 4670 Lab 3 9


!"# $"! $"# %"! %"#!"! &"!

'#!

'$!!

!

()*+,-./0

123*)-45678

7$7$()*+9$!:;2<$!41=>*?@)AB$8C&!9'$D"EF%

$!"!!G/0

Figure 15: ADS DSB modulator/demodulator output spectrum.

Agilent 33250A

Output

1.00000 MHz

To scope andPC speakers

Agilent 33250

?v pp

R C

1N4148

1 MHz Carrier1 kHz – 10 kHz Message@ 75% modulation index

ExternalAM via backport with musicsource (iPod)

Envelope detectorAM ModulationTransmitter

To 50 ohm port onspectrum analyzer

Figure 16: AM message recovery using an envelope detector.

9. Adjust the drive level to the diode envelope detector to be sufficient to overcome the diodeturn-on voltage of roughly 0.7 v. Initially include only the R value so you can better see thatthe diode is indeed halfwave rectifying the AM signal.

10. Choose a value for C so that the RC filtering action allows recovery of sinusoidal messagesignals up to 10 kHz. There is a trade-off involved here, as you will see when you observe thewaveform on the scope. We have capacitor substitution boxes in the lab which may be useful

ECE 4670 Lab 3 10

1.3 Appendix A: SRA-3+ Data Sheet

in the optimization process. Listen to the demodulated sinusoidal tone using the powered PCspeakers found at each lab station.

11. On the rear of the Agilent 33250 there is a connector that allows an external modulationsignal to be applied. Configure a music source, PC radio, iPod, etc as a source that candrive this rear connector. The modulation index will no longer be calibrated, so will haveto manually adjust the input audio level to keep the modulation index roughly below 100%.Comment on the quality of the recovered AM modulation using the PC speakers. Changethe carrier frequency from 1 MHz up 2 MHz. Observe that the performance should be aboutthe same? Why?

12. Frequency translation and the super-heterodyne principle, are fundamental to the design ofradio receivers. For efficient signal processing, it is best if we can design the receiver to havehigh gain and good frequency selectivity, at a fixed frequency. Translated a range of carrierfrequencies to a common intermediate frequency (IF) using a local oscillator (LO) is whatis usually done. In AM radio broadcasting, where the carrier frequency ranges from 540 –1600 kHz, a popular IF frequency is 455 kHz. A simple frequency translation for convertingreceived AM radio signals to 455 kHz is shown in Figure 17. The LO may use low-side orhigh-side tuning.

13. For a carrier frequency at 1 MHz and fIF D 455 kHz, what are the two possible values forfLO? What are the image frequencies associated with these LO frequencies, respectively.

14. Following the mixer is a simple bandpass filter created using an LC tank circuit. The circuititself is contained in a small metal package to provide RF shielding. A ferrite tuning slug(screw driver slot) at the top of the package, provides a means for fine tuning the tank centerfrequency. Probe with the scope at this point and observe that the amplitude of the receivedsignal goes up and down as you change the LO frequency about the nominal fLO.

15. To complete the receiver build up the op-amp based envelope detector shown in Figure 17.Set up the RC filter at the output of the envelope detector to allow recovery of up 5 kHzmessage signals.

16. Initially Listen and observe to the output with a 1 kHz message signal. As you vary/tune theLO what you see and hear should be like tuning an AM radio. Confirm this behavior.

17. Lastly repeat above using a music source via the external AM modulation input.

1.3 Appendix A: SRA-3+ Data SheetThe complete SRA-3+ data sheet is shown in Figure 18 and Figure 19.

1.4 Appendix B: Toko S7AG-A033HM 455 kHz Tank CircuitElectrical and Mechanical details of the 455 kHz tank circuit is shown in Figure 20

ECE 4670 Lab 3 11

1.4 Appendix B: Toko S7AG-A033HM 455 kHz Tank Circuit

Agilent 33250A

Output

1.00000 MHz

Agilent 33120A

Output

100.000 kHz

SRA-3+IF

LO

RF

To 50 ohm porton spectrum

Agilent 33250

Agilent 33120

500mv pp

2v ppfLO = ?

1 MHz Carrier1 kHz – 10 kHz Message@ 75% modulation index L =

65 –95 uh

C =1365 pf

Tankresonanceat 455 kHz

1 kohm

analyzer orToko S7AG-A033HM

Probe with Scope

50 ohm term.

To scope andPC speakers

R C

1N4148

Op-amp based

+–

1 kohm

1 kohm

1 kohm

Detector RC Filterdesign for 3dB cuttoffof 5 kHz

Envelope detector

1/2 LF353or similar

Figure 17: Frequency translation to a 455 KHz IF followed by a455 kHz bandpass filter using anLC tank circuit.

ECE 4670 Lab 3 12


Page 1 of 2

ISO 9001 ISO 14001 AS 9100 CERTIFIEDMini-Circuits®

P.O. Box 350166, Brooklyn, New York 11235-0003 (718) 934-4500 Fax (718) 332-4661 The Design Engineers Search Engine Provides ACTUAL Data Instantly at ®

Notes: 1. Performance and quality attributes and conditions not expressly stated in this specification sheet are intended to be excluded and do not form a part of this specification sheet. 2. Electrical specifications and performance data contained herein are based on Mini-Circuit’s applicable established test performance criteria and measurement instructions. 3. The parts covered by this specification sheet are subject to Mini-Circuits standard limited warranty and terms and conditions (collectively, “Standard Terms”); Purchasers of this part are entitled to the rights and benefits contained therein. For a full statement of the Standard Terms and the exclusive rights and remedies thereunder, please visit Mini-Circuits’ website at www.minicircuits.com/MCLStore/terms.jsp.

For detailed performance specs & shopping online see web site

minicircuits.comIF/RF MICROWAVE COMPONENTS

Level 7 (LO Power +7 dBm) 0.025 to 200 MHz

Frequency MixerPlug-In

CASE STYLE: A01PRICE: $20.20 ea. QTY (1-9)

Outline Dimensions ( )inchmm

Maximum Ratings

Pin ConnectionsLO 8

RF 1

IF 3,4^

GROUND 2,5,6,7

CASE GROUND 2

Outline Drawing

Electrical Specifications

REV. AM98898SRA-3+DJ/TD/CP/AM091006

1 dB COMP.: +1 dBm typ.

FREQUENCY (MHz)

CONVERSION LOSS(dB)

LO-RF ISOLATION(dB)

LO-IF ISOLATION(dB)

LO/RF IFMid-Band

m Total RangeMax.

L M U L M U

fL-fU—X Max. Typ. Min. Typ. Min. Typ. Min. Typ. Min. Typ. Min. Typ. Min.

.025-200 DC-200 4.61 .06 7.5 8.5 60 50 45 35 35 25 45 35 40 30 30 20

Frequency(MHz)

Conversion Loss (dB)

Isolation L-R(dB)

IsolationL-I

(dB)

VSWR RF Port

(:1)

VSWR LO Port

(:1)

RF LOLO

+7dBmLO

+7dBmLO

+7dBmLO

+7dBmLO

+7dBm

Typical Performance Data

Electrical Schematic

SRA-3+

L = low range [fL to 10 fL] M = mid range [10 fL to fU/2] U = upper range [fU/2 to fU]m= mid band [2fL to fU/2]

Features

Applications

Operating Temperature -55°C to 100°C

Storage Temperature -55°C to 100°C

RF Power 50mW

IF Current 40mA

^ pins must be connected together externally

A B C D E F.770 .800 .385 .400 .370 .400

19.56 20.32 9.78 10.16 9.40 10.16G H J K wt

.200 .20 .14 .031 grams5.08 5.08 3.56 0.79 5.2

+ RoHS compliant in accordance with EU Directive (2002/95/EC)

The +Suffix has been added in order to identify RoHS Compliance. See our web site for RoHS Compliance methodologies and qualifications.

0.025 30.03 6.94 58.72 53.27 1.16 2.06 0.04 30.04 5.80 55.35 51.43 1.17 2.04 0.05 30.05 5.52 54.61 51.09 1.17 2.01 0.10 30.10 5.16 53.51 50.41 1.16 1.99 0.20 30.20 4.98 53.27 50.18 1.16 2.05 0.50 30.50 4.92 53.12 50.13 1.15 2.08 1.00 31.00 4.82 53.18 50.48 1.15 2.07 2.00 32.00 4.77 53.13 50.55 1.14 2.07 5.00 35.00 4.76 53.42 50.99 1.13 2.05 10.00 40.00 4.81 53.68 51.27 1.11 2.02 20.00 50.00 4.87 53.67 50.52 1.10 2.02 38.48 68.48 4.96 53.25 48.52 1.09 2.02 50.00 80.00 4.94 53.49 47.54 1.09 2.03 69.25 99.25 4.90 53.53 45.77 1.08 2.03 84.63 54.63 4.86 53.31 44.13 1.09 2.05 100.00 70.00 4.81 53.55 42.70 1.11 2.07 123.09 93.09 4.87 55.31 40.58 1.13 2.11 153.85 123.85 4.96 52.97 38.04 1.15 2.13 176.93 146.93 5.19 49.53 38.76 1.18 2.14 200.00 170.00 5.28 45.61 38.31 1.21 2.15

Figure 18: Mini-Circuits SRA-3+ data sheet

ECE 4670 Lab 3 13


Page 2 of 2

ISO 9001 ISO 14001 AS 9100 CERTIFIEDMini-Circuits®

P.O. Box 350166, Brooklyn, New York 11235-0003 (718) 934-4500 Fax (718) 332-4661 The Design Engineers Search Engine Provides ACTUAL Data Instantly at ®

Notes: 1. Performance and quality attributes and conditions not expressly stated in this specification sheet are intended to be excluded and do not form a part of this specification sheet. 2. Electrical specifications and performance data contained herein are based on Mini-Circuit’s applicable established test performance criteria and measurement instructions. 3. The parts covered by this specification sheet are subject to Mini-Circuits standard limited warranty and terms and conditions (collectively, “Standard Terms”); Purchasers of this part are entitled to the rights and benefits contained therein. For a full statement of the Standard Terms and the exclusive rights and remedies thereunder, please visit Mini-Circuits’ website at www.minicircuits.com/MCLStore/terms.jsp.

For detailed performance specs & shopping online see web site

minicircuits.comIF/RF MICROWAVE COMPONENTS

0.025 30.03 6.94 58.72 53.27 1.16 2.06 0.04 30.04 5.80 55.35 51.43 1.17 2.04 0.05 30.05 5.52 54.61 51.09 1.17 2.01 0.10 30.10 5.16 53.51 50.41 1.16 1.99 0.20 30.20 4.98 53.27 50.18 1.16 2.05 0.50 30.50 4.92 53.12 50.13 1.15 2.08 1.00 31.00 4.82 53.18 50.48 1.15 2.07 2.00 32.00 4.77 53.13 50.55 1.14 2.07 5.00 35.00 4.76 53.42 50.99 1.13 2.05 10.00 40.00 4.81 53.68 51.27 1.11 2.02 20.00 50.00 4.87 53.67 50.52 1.10 2.02 38.48 68.48 4.96 53.25 48.52 1.09 2.02 50.00 80.00 4.94 53.49 47.54 1.09 2.03 69.25 99.25 4.90 53.53 45.77 1.08 2.03 84.63 54.63 4.86 53.31 44.13 1.09 2.05 100.00 70.00 4.81 53.55 42.70 1.11 2.07 123.09 93.09 4.87 55.31 40.58 1.13 2.11 153.85 123.85 4.96 52.97 38.04 1.15 2.13 176.93 146.93 5.19 49.53 38.76 1.18 2.14 200.00 170.00 5.28 45.61 38.31 1.21 2.15

Performance ChartsSRA-3

CONVERSION LOSS

4.0

4.5

5.0

5.5

6.0

6.5

7.0

7.5

8.0

0.01 0.1 1 10 100 1000FREQUENCY (MHz)

CO

NV

ER

SIO

N L

OS

S (d

B) LO=+4 dBm LO=+7 dBm LO=+10 dBm

at IF Freq of 30 MHz

SRA-3L-R ISOLATION

30

40

50

60

70

80

0 40 80 120 160 200FREQUENCY (MHz)

ISO

LATI

ON

(dB

)

LO=+4 dBm LO=+7 dBm LO=+10 dBm

SRA-3RF VSWR

1.0

1.1

1.2

1.3

1.4

1.5

0 40 80 120 160 200FREQUENCY (MHz)

VS

WR


SRA-3L-I ISOLATION

2025303540455055606570

0 40 80 120 160 200FREQUENCY (MHz)

ISO

LATI

ON

(dB

)


SRA-3LO VSWR

1.0

1.5

2.0

2.5

3.0

3.5

4.0

0 40 80 120 160 200FREQUENCY (MHz)

VS

WR


SRA-3IF VSWR

1.0

1.5

2.0

2.5

3.0

0 40 80 120 160 200FREQUENCY (MHz)

VS

WR


SRA-3+

Figure 19: Mini-Circuits SRA-3+ data sheet continued.

ECE 4670 Lab 3 14


Figure 20: Toko S7AG-A033HM 455 kHz tank circuit detail.

ECE 4670 Lab 3 15

ece 4670 spring 2014 lab 3 mixers and amplitude...

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