harmonic treatment in industrial power
TRANSCRIPT
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IEEE PESC-02 JUNE 2002 1
HARMONIC TREATMENT IN INDUSTRIAL POWER SYSTEMS
Presented by
Stefanos Manias
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JUNE 2002 IEEE PESC-02 2
CONTACT INFORMATION
Stefanos N. Manias
National Technical University of Athens
Phone: +3010-7723503
FAX: +3010-7723593
E-mail: [email protected]
Mailing Address
National Technical University of Athens
Department of Electrical and Computer Engineering
9, Iroon Polytechniou Str, 15773 Zografou
Athens, Greece
mailto:[email protected] -
JUNE 2002 IEEE PESC-02 3
PLAN OF PRESENTATION
1. DEFINITIONS
2. CATEGORIES OF POWER QUALITY VARIATIONS
3. HARMONIC DISTORTION SOURCES IN INDUSTRIAL POWER
SYSTEMS
4. EFFECTS OF HARMONICS ON ELECTRICAL EQUIPMENT
5. HARMONIC MEASUREMENTS IN INDUSTRIAL POWER SYSTEMS
6. HARMONIC STANDARDS
7. HARMONIC MITIGATING TECHNIQUES
8. GENERAL PASSIVE AND ACTIVE FILTER DESIGN PROCEDURES
9. DESIGN EXAMPLES
10. CONCLUSIONS
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JUNE 2002 IEEE PESC-02 4
WHY HARMONIC ANALYSIS ?
When a voltage and/or current waveform is distorted, it causes abnormal operating conditions in a power system such as:
Voltage Harmonics can cause additional heating in induction and
synchronous motors and generators.
Voltage Harmonics with high peak values can weaken insulation in
cables, windings, and capacitors.
Voltage Harmonics can cause malfunction of different electronic
components and circuits that utilize the voltage waveform for
synchronization or timing.
Current Harmonics in motor windings can create Electromagnetic
Interference (EMI).
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JUNE 2002 IEEE PESC-02 5
Current Harmonics flowing through cables can cause higher
heating over and above the heating that is created from the
fundamental component.
Current Harmonics flowing through a transformer can cause
higher heating over and above the heating that is created by the
fundamental component.
Current Harmonics flowing through circuit breakers and switch-
gear can increase their heating losses.
RESONANT CURRENTS which are created by current harmonics
and the different filtering topologies of the power system can
cause capacitor failures and/or fuse failures in the capacitor or
other electrical equipment.
False tripping of circuit breakers ad protective relays.
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JUNE 2002 IEEE PESC-02 6
a) Current Source nonlinear load
Diode rectifier for ac drives,
electronic equipment, etc
HARMONIC SOURCES
Thyristor rectifier for dc drives,
heater drives, etc.
Per-phase equivalent circuit
of thyristor rectifier
b) Voltage source nonlinear load
Per-phase equivalent circuit
of diode rectifier
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JUNE 2002 IEEE PESC-02 7
010 20 30 40
-1.0
-0.5
0.0
0.5
1.0
Time (mS)
Curr
ent
010 20 30 40
-1.0
-0.5
0.0
0.5
1.0
Time (mS)
Curr
ent
010 20 30 40
-1.0
-0.5
0.0
0.5
1.0
Time (mS)
Curr
en
t
TYPE OF
NONLINEAR LOAD
TYPICAL WAREFORM
THD%
1-
Uncontrolled
Rectifier
80%
(high 3rd
component)
1-
Semicontrolled
Rectifier Bridge
2nd, 3rd, 4th ,......
harmonic
components
6 Pulse Rectifier
with output voltage
filtering and without
input reactor filter
80%
5, 7, 11, .
INPUT CURRENT OF DIFFERENT
NOLINEAR LOADS
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JUNE 2002 IEEE PESC-02 8
010 20 30 40
-1.0
-0.5
0.0
0.5
1.0
Time (mS)
Curr
ent
0 10 20 30 40-1.0
-0.5
0.0
0.5
1.0
Time (mS)
Cu
rren
t
0 10 20 30 40-1.0
-0.5
0.0
0.5
1.0
Time (mS)
Cu
rren
t
6 - Pulse Rectifier
with large output
inductor
28%
5, 7, 11, ..
6 - Pulse Rectifier
with output voltage
filtering and with 3%
reactor filter or with
continues output
current
40%
5, 7, 11, ..
12 - Pulse Rectifier
15%
11, 13, ..
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JUNE 2002 IEEE PESC-02 9
CURRENT HARMONICS GENERATED BY 6-PULSE CSI CONVERTERS
HARMONIC
P.U PULSE
1
1.00
5
0.2
7
0.143
11
0.09
13
0.077
17
0.059
19
0.053
23
0.04
CURRENT HARMONICS GENERATED BY 12-PULSE CSI CONVERTERS
HARMONIC
P.U PULSE
IEEE 519 std
1
1.00
-
5
0.03-0.06
5.6%
7
0.02-0.06
5.6%
11
0.05-0.09
2.8%
13
0.03-0.08
2.8%
THD
7.5%-14.2%
7.0%
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JUNE 2002 IEEE PESC-02 10
RECENT CURRENT MEASUREMENTS TAKEN IN AN
INDUSTRIAL PLANT WITH 600 KVA, 20 KV/400 V
DISTRIBUTION TRANFORMER
Current waveform and its respective spectrum
at the inputs of a motor drive system
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JUNE 2002 IEEE PESC-02 11
Current waveform and its respective spectrum
at the inputs of a motor drive system
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JUNE 2002 IEEE PESC-02 12
Current waveform and its respective spectrum
at the secondary of the distribution transformer
( i.e. at the service entrance)
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JUNE 2002 IEEE PESC-02 13
DEFINITIONS
f (t) = Fourier Series of a periodic function f (t) =
1hhho th cosCC (1)
T
oodttf
T
1C ,)( (2)
T
ohdt)thcos()t(f
T
2A (3)
T
oh dt)thsin()t(f
T
2B (4)
h = harmonic order
2h
2hh BAC
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JUNE 2002 IEEE PESC-02 14
%THD
100V
V
1
2h
2h
(5)
%iTHD
100I
I
1
2h
2
h
(6)
Percentage of the Total Harmonic Distortion of
a nonsinusoidal voltage waveform
Percentage of the Total Harmonic Distortion of
a nonsinusoidal current waveform
hthVh
hthIh
harmonic component of the voltage
harmonic component of the current
V~
H RMS value of the voltage distortion V~
2h
2h
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JUNE 2002 IEEE PESC-02 15
I~
1h
2hI
~ (7)
V~
V~
1h
2
h
(8)
100VAk SC
kVA DriveHF %THD (9)
15h
2h
2 I/Ih (10)
RMS value of a nonsinusoidal current =
RMS value of a nonsinusoidal voltage =
HF Harmonic Factor =
I~H RMS value of the current distortion
I~
2h
2h
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JUNE 2002 IEEE PESC-02 16
kVA Drive
kVA SC
SINUSOIDAL VOLTAGE NONSINUSOIDAL CURRENT
1i,1 cosI~ V
~P
I~ V
~S , sinI
~ V
~Q 1i,1
(11)
(12)
(13)
Full load kVA rating of the Drive system
Short Circuit kVA of the distribution system at
the point of connection
222 QPS VA DistortionD
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JUNE 2002 IEEE PESC-02 17
2h
2h,i
221,i
222 I~
V~
I~
V~
SD (14)
S
PFactor Power True 1
1,icos
I
I(15)
Factorment Displace Factor Distortion
NONSINUSOIDAL VOLTAGE AND NONSINUSOIDAL CURRENT
1h 1hhhh , hhh sinI
~V~
QcosI~
V~
P (16)
SSSSPower DistortionD
mnm n
*mn
*nm
mnmn
nm (17)
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JUNE 2002 IEEE PESC-02 18
2222 DQPS(18)
2 N
21
2
HH
2
1H
2
H1
2
11
1h
2h
2h
SS I~
V~
I~
V~
I~
V~
I~
V~
I~
V~
S
(19)
111 I~
V~
PowerApparent lFundamenta S
PowerApparent ntalNonfundame SN
2HH
21H
2H1
2N I
~V~
I~
V~
I~
V~
S
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JUNE 2002 IEEE PESC-02 19
Power DistortionCurrent I~
V~
H1 (20)
Power Distortion Voltage I~
V~
1H (21)
PowerApparent Harmonic I~
V~
HH (22)
Power ActiveNon Harmonic Total
Power Active Harmonic Total NP S 2H2H
2H (23)
phase32
L-LC VAR/V capacitor theof Reactance X
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JUNE 2002 IEEE PESC-02 20
Harmonic sequence is the phase rotation relationship with respect to the fundamental component.
Positive sequence harmonics ( 4th, 7th, 10th , . (6n+1) th ) have the same phase rotation as the fundamental component. These harmonics circulate between the phases.
Negative sequence harmonics ( 2nd, 5th, 8th (6n-1) th ) have the opposite phase rotation with respect to the fundamental component. These harmonics circulate between the phases.
Zero sequence harmonics ( 3rd, 6th, 9th, .. (6n-3) th ) do not produce a rotating field. These harmonics circulate between the phase and neutral or ground. These third order or zero sequence harmonics, unlike positive and negative sequence harmonic currents, do not cancel but add up arithmetically at the neutral bus.
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JUNE 2002 IEEE PESC-02 21
EXAMPLE 1
A periodic, sinusoidal voltage of instantaneous value tsin2200v
Is applied to a nonlinear load impedance. The resulting instantaneous current is
given by: ooo 60t3sin1060t2sin1045tsin202i
Calculate the components P, Q, D of the apparent voltamperes and hence calculate the displacement factor, the distortion factor and the power factor.
Solution
tsin2200v
ooo 60t3sin1060t2sin1045tsin202i
The presence of the nonlinearity causes frequency components of current (i.e. the
second and third harmonic terms) that are not present in the applied voltage.
The rms voltage and current at the supply are:
V200V~
2222 101020I~
22A106
SINUSOIDAL VOLTAGE -NONSINIMUSOIDAL CURRENT
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JUNE 2002 IEEE PESC-02 22
The apparent voltamperes at the input is therefore given by
2622222 VA1024106200I~
V~
S
In this example only the fundamental frequency components are common to
both voltage and current. Therefore, the real power P and the apparent
power Q are
11cosI~
V~
P
o45cos20200
W2
4000
11sinI~
V~
Q
o45sin20200
VA2
4000
1 = displacement angle between the fundamental of the voltage and the fundamental of the current
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JUNE 2002 IEEE PESC-02 23
21
222 I~
I~
V~
D
232
2 I~
I~
V~
26222 VA1081010200
22222 I~
V~
DQP
Displacement factor 707.02
1cos 1
Distortion factor 817.0600
20
I
I1
Therefore, the power factor is
577.06
2
2
1PF
1111 cosI
I~
I~
V~cosI
~V~
S
Pfactorpower PF
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JUNE 2002 IEEE PESC-02 24
EXAMPLE 2
A periodic, sinusoidal voltage given by o30t5sin200tsin2002vis applied to a series, linear, resistance-inductance load of resistance 4 and
fundamental frequency reactance 10.
Calculate the degree of power factor improvement realizable by capacitance
Solution. The rms terminal voltage is given by
25
21 V
~V~
V~
Compensation when .HZ50f1
22 200200
V~
Therefore
V283V~
10j4Z1
8.10Z1
o2.684/10tan 11
NONSINUSOIDAL VOLTAGE -RL LOAD
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JUNE 2002 IEEE PESC-02 25
505 15
50j4Z5
50Z5o1
5 4.854/50tan
The instantaneous load current is given by
ooo 4.8530t5sin50
2002.68tsin
8.10
2002i
The rms load current I~
is therefore given by
2
5
5
2
1
12
5
2
1
2
Z
V~
Z
V~
I~
I~
I~
222 A359452.18
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JUNE 2002 IEEE PESC-02 26
Average power P In this case is
...cosI~
V~
cosI~
V~
cosI~
V~
Pn
1
222111Lnn
oo 4.85cos42002.68cos52.18200
W1440
The power factor before compensation is therefore
27.01072.28
1440
S
PPF
6
26222 VA1072.28I~
V~
S
Apparent voltamperes S at the load terminals in the absence of capacitance is
therefore
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JUNE 2002 IEEE PESC-02 27
EXAMPLE 3
A periodic, nonsinusoidal voltage with instantaneous value given by
o30-t2sin200tsin2002v
Solution.
is applied to a nonlinear impedance.
The resulting current has an instantaneous value given by ooo
L 60t3sin1060t2sin1045tsin202i
Calculate the components LDLXLR S,S,S of the load apparent voltamperes
and compare thee with the classical values LLL D,Q,P respectively.
o30-t2sin200tsin2002v
oooL 60t3sin1060t2sin1045tsin202i
Note that the presence of the load nonlinearity causes a frequency component
of load current (I.e. the third harmonic term) that is not present in the supply
voltage.
NONSINUSOIDAL VOLTAGE AND NONSINIMUSOIDAL CURRENT
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JUNE 2002 IEEE PESC-02 28
The rms voltage and current at the supply are given by
24222 V108200200V~
222222L A106101020I
~
The load apparent voltamperes LS therefore has a value defined in terms V~
and LI
~
262
L
22
L VA1048I~
V~
S
Instantaneous expressions of the hypothetical currents DXR i,i,i are given by
o0o
R 30t2sin30cos10tsin45cos202i
222o2o2
LR A104
1130cos1045cos20I
~
o0oX 30t2cos30sin10tcos45sin202i
222o2o2
LX A104
930sin1045sin20I
~
o
D 60t3sin10 2i
222
LD A10I~
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JUNE 2002 IEEE PESC-02 29
Note that current components XR i,i contain only those harmonic terms which are common to both voltage and current. These are therefore consistent with the
1n terms.
The rms load current components LDLXLR I~
,I~
,I~
are found, as expected to sum
to the total rms load current LI~
2
L
222
LD
2
LR
2
LD I~
1064
9
4
11110I
~I~
I~
Components LDLXLR S,S,S of the apparent voltamperes can now be obtained
26422
LR
22
LR VA1022108104
11I~
V~
S
26422
LX
22
LX VA1018108104
9I~
V~
S
26422
LD
22
LD VA10810810I~
V~
S
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JUNE 2002 IEEE PESC-02 30
The component voltamperes are seen to sum to the total apparent voltamperes
8182210SSS 62LD2LX
2LR
26 VA1048
2
LS
Components LLL D,Q,P of LS are found as follows: 2
n
1
1n1n1n2L cosI
~V~
P
2oo 30cos1020045cos20200
22 310220100
2
LR
662
6 S108.2064381032210
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JUNE 2002 IEEE PESC-02 31
2n
1
1n1n1n2L sinI
~V~
Q
2oo 30sin1020045sin20200
2
LX
66 S106.1412210
2L
2L
2L
2L QPSD
2LD
266 SVA106.12106.148.2048
From the possible compensation viewpoint it is interesting to note that LXS
and LQ differ by significant amount.
LXS could be defined as that component of the load apparent voltamperes that
Is obtained by the combination of supply voltage harmonics with quadrature
Components of corresponding frequency load current harmonics.
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JUNE 2002 IEEE PESC-02 32
Similarly the definition of active voltamperes LRS could be given by that
component of the load apparent voltamperes that is obtained by the combination
of supply voltage harmonics with in-phase components of corresponding
frequency load current harmonics.
Both LRS and LXS are entirely fictitious and non-physical. The active
voltamperes LRS Is not to be compares in importance with the average power
LP which is a real physical property of the circuit. Term LRS Is merely the
analytical complement of term LXS
Term LXS the energy-storage reactive voltamperes, is that component
of the load apparent voltamperes that can be entirely compensated (for sinusoidal
supply voltage) or minimized (for nonsinusoidal supply voltage) by energy-storage
methods.
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JUNE 2002 IEEE PESC-02 33
Voltage and current profiles in a
commercial building
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JUNE 2002 IEEE PESC-02 34
HARMONIC STANDARDS
International Electrotechnical Commission (IEC) European
Standards.
- EN 61000-3-2 Harmonic Emissions standards were first published
as IEC 55-2 1982 and applied only to household appliances. It was
revised and reissued in 1987 and 1995 with the applicability
expanded to include all equipment with input current 16A per
phase. However, until January 1st, 2001 a transition period is in
effect for all equipment not covered by the standard prior to 1987.
- The objective of EN 61000-3-2 (harmonics) is to test the equipment
under the conditions that will produce the maximum harmonic
amplitudes under normal operating conditions for each harmonic
component. To establish limits for similar types of harmonics current
distortion, equipment under test must be categorized in one of the
following four classes.
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JUNE 2002 IEEE PESC-02 35
CLASS-A: Balanced three-phase equipment and all other equipment
except that stated in one of the remaining three classes.
CLASS-B: Portable electrical tools, which are hand held during normal
operation and used for a short time only (few minutes)
CLASS-C: Lighting equipment including dimming devices.
CLASS-D: Equipment having an input current with special wave shape
( e.g.equipment with off-line capacitor-rectifier AC input
circuitry and switch Mode power Supplies) and an active
input power 600W.
- Additional harmonic current testing, measurement techniques and
instrumentation guidelines for these standards are covered in IEC
1000-4-7.
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JUNE 2002 IEEE PESC-02 36
IEEE 519-1992 United States Standards on harmonic limits
- IEEE limits service entrance harmonics. - The IEEE standard 519-1992 limits the level of harmonics at the
customer service entrance or Point of Common Coupling (PCC).
- With this approach the costumers current distortion is limited based on relative size of the load and the power suppliers voltage
distortion based on the voltage level.
IEEE 519 and IEC 1000-3-2 apply different philosophies, which
effectively limit harmonics at different locations. IEEE 519 limits
harmonics primarily at the service entrance while IEC 1000-3-2 is
applied at the terminals of end-user equipment. Therefore, IEC limits
will tend to reduce harmonic-related losses in an industrial plant
wiring, while IEEE harmonic limits are designed to prevent
interactions between neighbors and the power system.
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JUNE 2002 IEEE PESC-02 37
POWER QUALITY STANDARDS
IEEE 519-1992 STANDARDS
TABLE I CURRENT DISTORTION LIMITS FOR GENERAL DISTRIBUTION SYSTEMS
(120-69000 V)
Isc/IL
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JUNE 2002 IEEE PESC-02 38
TABLE II
LOW VOLTAGE SYSTEM CLASSIFICATION AND DISTORTION LIMITS
IEEE 519-1992 STANDARTS
Special
Applications
General
System
Dedicated
System
Notch Depth 10% 20% 50%
THD (Voltage) 3% 5% 10%
Notch Area
(AN)*
16,400 22,800 36,500
Source: IEEE Standard 519-1992.
Note: The value AN for another than 480Volt systems should be
multiplied by V/480 .
The notch depth, the total voltage distortion factor (THD) and
the notch area limits are specified for line to line voltage.
In the above table, special applications include hospitals and
airports. A dedicated system is exclusively dedicated to converter load.
*In volt-microseconds at rated voltage and current.
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JUNE 2002 IEEE PESC-02 39
TABLE III
LIMITS OF THD%
IEEE 519-1992 STANDARDS
SYSTEM
Nominal Voltage
Special
Application
General
Systems
Dedicated
Systems
120-600V 3.0 5.0 8.0
69KV and below - 5.0 -
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JUNE 2002 IEEE PESC-02 40
TABLE IV PROPOSED IEC 555-2 CLASS D STANDARDS for power from 50 to 600W
Harmonic Relative limits
Milliamps/Watt
Absolute Limits
Amps
3 3.4 2.30
5 1.9 1.14
7 1.0 0.77
9 0.5 0.40
11 0.35 0.33
13 linear
extrapolation
0.15 (15/n)
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JUNE 2002 IEEE PESC-02 41
METHODOLOGY FOR COMPUTING DISTORTION
Step 1: Compute the individual current harmonic distortion at each dedicated bus using different Software programs (i.e. SIMULINK, SPICE, e.t.c.) or tables that provide the current distortion of nonlinear loads.
Step 2: Compute the voltage and current harmonic content at the Point of Common Coupling (PCC) which is located at the input of the industrial power system.
- Each individual harmonic current at the PCC is the sum of harmonic current contribution from each dedicated bus.
- The load current at PCC is the sum of the load current contribution from each dedicated bus.
- The maximum demand load current at PCC can be found by computing the load currents for each branch feeder and multiply by a demand factor to obtain feeder demand. Then the sum of all feeder demands is divided by a diversity factor to obtain the maximum demand load current.
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JUNE 2002 IEEE PESC-02 42
Step 3: Choose a base MVA and base KV for the system use the following
equations in order to compute individual and total current and
voltage harmonic distortions at PCC and any other point within the
power system.
Ib= Base current in Amps Ampsb
3b
kV3
10MVA
= System impedance = p.u. MVA
MVA
sc
b
MVAb= Base MVA, MVAsc= short circuit MVA at the point of interest
VH= Percent individual harmonic voltage distortion =
Volts 100ZhI
Is
b
h
(24)
(25)
(26)
sZ
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JUNE 2002 IEEE PESC-02 43
h = harmonic order
100V
21V
%THD1
2h
2h
100I
I
%THD1
2
2h
2h
i
IH = Percent individual harmonic distortion = 100I
I
L
h
Isc = Short Circuit current at the point under consideration.
IL = Estimated maximum demand load current
S.C. Ratio = Short circuit Ratio
D
sc
L
sc
MVA
MVA
I
I
MVAD = Demand MVA
(27)
(28)
(29)
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JUNE 2002 IEEE PESC-02 44
K Factor = Factor useful for transformers design and
specifically from transformers that feed
Adjustable Speed Drives
1h
2
L
h2
I
Ih
ONCE THE SHORT CIRCUIT RATIO IS KNOWN, THE IEEE CURRENT
HARMONIC LIMITS CAN BE FOUND AS SPECIFIED IN TABLE I OF
THE IEEE 519-1992 POWER QUALITY STANDARDS
USING THE ABOVE EQUATIONS VALUES OF IDIVINDUAL AND
TOTAL VOLTAGE AND CURRENT HARMONIC DISTORTION CAN
BE COMPUTED AND COMPARED WITH THE IEEE LIMITS
(30)
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JUNE 2002 IEEE PESC-02 45
Step 4: If the analysis is being performed for CSI-type drives then the area
of the voltage notch AN should also be computed.
- At this point an impedance diagram of the under analysis
industrial power system should be available.
- The Notch Area AN at the PCC can be calculated as follows.
AN = AN1 + AN2 + . V . microsec
AN1 , AN2 , are the notch areas contribution of the different busses
ANDR1 : Notch area at the input of the drive
1NDR1N Adrive the toPCC from sinductance of sum the inductance Source
inductance SourceA
(31)
(32)
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JUNE 2002 IEEE PESC-02 46
Step 5: Determine preliminary filter design.
Step 6: Compute THDv and THDi magnitudes and impedance versus
frequency plots with filters added to the system, one at a time.
SIMULINK or PSPICE software programs can be used for final
adjustments.
Step 7: Analyze results and specify final filter design.
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JUNE 2002 IEEE PESC-02 47
EXAMPLE OF A SYSTEM ONE LINE
DIAGRAM
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JUNE 2002 IEEE PESC-02 48
System impedances diagram which can be used to
calculate its resonance using PSPICE or SIMULINK
programs
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JUNE 2002 IEEE PESC-02 49
1) Parallel-passive filter for current-source nonlinear loads
TYPES OF FILTERS
Harmonic Sinc
Low Impedance
Cheapest
VA ratings = VT (Load Harmonic current + reactive current of the filter)
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JUNE 2002 IEEE PESC-02 50
2) Series-passive filter for voltage-source nonlinear loads
Harmonic dam High-impedance
Cheapest
VA ratings = Load current (Fundamental drop across filter + Load Harmonic Voltage)
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JUNE 2002 IEEE PESC-02 51
3) Basic parallel-active filter for current source in nonlinear loads
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JUNE 2002 IEEE PESC-02 52
4) Basic series-active filter for voltage-source in nonlinear loads
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JUNE 2002 IEEE PESC-02 53
5) Parallel combination of parallel active and parallel passive
6) Series combination of series active and series passive
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JUNE 2002 IEEE PESC-02 54
7) Hybrid of series active and parallel passive
8) Hybrid of parallel active and series passive
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JUNE 2002 IEEE PESC-02 55
9) Series combination of parallel-passive and parallel-active
10) Parallel combination of series-passive and series-active
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JUNE 2002 IEEE PESC-02 56
11) Combined system of series-active and parallel-active
12) Combined system of parallel-active and series-active
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JUNE 2002 IEEE PESC-02 57
A SIMPLE EXAMPLE OF AN INDUSTRIAL
POWER DISTRIBUTION SYSTEM
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JUNE 2002 IEEE PESC-02 58
HARMONIC LIMITS EVALUATION WHEN POWER-FACTOR-CORRECTION CAPASITORS
ARE USED
- As it can be seen from the power distribution circuit the power-factor-
correction capacitor bank, which is connected on the 480 Volts bus, can
create a parallel resonance between the capacitors and the system
source inductance.
- The single phase equivalent circuit of the distribution system is shown
below.
Using the above circuit the following equations hold:
Source AC
totL SI
C
inZ
hI
fI
SV
HarmonicLoad
totR
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JUNE 2002 IEEE PESC-02 59
, R
Xtancos
MVA
kVR 1
sc
2LL
sys 2
syssys
RR
, R
Xtansin
MVA
kVX 1
sc
2LL
sys2
syssys
XX
tr
2LL
putrkVA
kV1000RR
tr
2LL
putrkVA
kV1000XX
= The turns ratio of the transformer at PCC
(33)
(34)
(35)
(36)
-
JUNE 2002 IEEE PESC-02 60
trsystot XXX
cap
2cap
ckVAR
kV1000X
X
L tottot f2
X tot
X
1C
c
C
1Xc
trsystot RRR (37)
(38)
(39)
(40)
(41)
(42)
-
JUNE 2002 IEEE PESC-02 61
C
1jLjR
C/jLjRZ
tottot
tottotin
, C
1L
ototo
oo
2
1f
The impedance looking into the system from the load, consists of the
parallel combination of source impedance and the
capacitor impedance tottotjXR
inZ
The equation for can be used to determine the equivalent system
impedance for different frequencies. The harmonic producing loads can
resonate (parallel resonance), the above equivalent circuit. Designating
the parallel resonant frequency by (rad/sec) or (HZ) and equating
the inductive and capacitive reactances.
inZ
o of
(43)
(44)
-
JUNE 2002 IEEE PESC-02 62
- Harmonic current components that are close to the parallel resonant frequency are amplified.
- Higher order harmonic currents at the PCC are reduced because the capacitors are low impedance at these frequencies.
- The figure below shows the effect of adding capacitors on the 480 Volts bus for power factor correction.
This figure shows that by adding some typical sizes of power factor correction capacitors will
result in the magnification of the 5th and 7th harmonic components, which in turns makes it
even more difficult to meet the IEEE 519-1992 harmonic current standards .
- Power factor correction capacitors should not be used without turning reactors in case the
adjustable speed drives are >10% of the plant load.
-
JUNE 2002 IEEE PESC-02 63
Let us examine an industrial plant with the following data:
- Medium voltage = 20KVLL
- Low voltage = 0.4 KVLL
- Utility three phase short circuit power = 250 MVA
- For asymmetrical current, the ratio of system impedance R
X 4.2
The Transformer is rated:
1000 KVA, 20 KV-400 Y/230 V
Rpu = 1%, Xpu = 7%
- The system frequency is: fsys = 50 HZ.
- For power factor correction capacitors the following cases are examined:
a. 200 KVAR
b. 400 KVAR
c. 600 KVAR
d. 800 KVAR
EXAMPLE
-
JUNE 2002 IEEE PESC-02 64
The parallel resonant frequencies for every case of power factor correction is calculated as follows:
6154.04.2tancos250
20R 1
2
sys
4769.14.2tansin250
20X 1
2
sys
504.0
20
000246.0506154.0R 2sys
000591.0504769.1X 2sys
00160.01000
4.0100001.0R
2
tr
0112.01000
4.0100007.0X
2
tr
-
JUNE 2002 IEEE PESC-02 65
001846.00016.0000246.0Rtot
011791.00112.0000591.0X tot
H1055.37502
011791.0L 6tot
Case a:
8.0200
4.01000X
2
c
F1098.38.0502
1C 3
HZ18.412
1098.31050.372
1f
36o
For 200 KVAR, the harmonic order at which parallel resonance occurs is:
24.85018.412h
-
JUNE 2002 IEEE PESC-02 66
Case b:
4.0400
4.01000X
2
c
F1096.7C 3
HZ45.291fo
83.5h
Case c:
267.0600
4.01000X
2
c
F1094.11C 3
HZ97.237fo
76.4h
-
JUNE 2002 IEEE PESC-02 67
Case d:
2.0800
4.01000X
2
c
F1092.15C 3
HZ08.206fo
12.4h
It is clear for the above system that in the 600 KVAR case, there
exists a parallel resonant frequency close to the 5th harmonic. of
-
JUNE 2002 IEEE PESC-02 68
POWER FACTOR CORRECTION AND HARMONIC TREATMENT USING TUNED FILTERS
- Basic configuration of a tuned 3- capacitor bank for power factor
correction and harmonic treatment.
Simple and cheap filter
Prevents of current harmonic magnification
-
JUNE 2002 IEEE PESC-02 69
- IN ORDER TO AVOID HARMONIC MAGNIFICATION WE CHOOSE A
TUNED FREQUENCY < FITH HARMONIC (i.e 4.7)
- The frequency characteristic of the tuned filter at 4.7 is shown below
As it can be seen from the above figure significant reduction of the 5th
harmonic is achieved. Moreover, there is some reduction for all the other
harmonic components.
-
JUNE 2002 IEEE PESC-02 70
The single phase equivalent circuit of the power distribution system
with the tuned filter is shown below
Using the above circuit the following equations hold:
-
JUNE 2002 IEEE PESC-02 71
0C
1LL
ofototo
21
ftot
oCLL2
1f
C1LLjR
LjRII
ftottot
tottothf
cap2
os
2cap
2os
c2
os
fkVARf2
kV1000f
f2
Xf2
f2C
1L
(parallel resonance)
= resonance frequency of the
equivalent distribution circuit
21
f
osCL2
1f = Resonant frequency of the series filter
The new parallel combination is having resonant frequency when
Also
(45)
(46)
(47)
(48)
-
JUNE 2002 IEEE PESC-02 72
C
1jLjLjR
C
1jLjLjR
Z
ftottot
ftottot
in
C
1LL jR
C
1jLjLjR
ftottot
ftottot
tottotsh LjRIV
C1LL jR
C/1L jII
ftottot
fhs (49)
(50)
(51)
-
JUNE 2002 IEEE PESC-02 73
As it was discussed before Selecting HZ235fo or 4.7 th harmonic
With KVcap= 0.4 , KVARcap= 600
H45.38H1045.686002352
4.0100050L 6
2
2
f
The new parallel combination is having resonant frequency:
CLL2
1f
ftoto
with H1055.37L 6tot
H1045.38L 6f
F1094.11C 3
we have
HZ16.167
1094.1110762
1f
36o
43.350/16.167h (without Lf was 4.76)
-
JUNE 2002 IEEE PESC-02 74
The following table shows the variation of Parallel resonant frequency
With and without resonant inductor
KVAR
C(mF)
Parallel Resonant f0
Without Lf With Lf
200 3.98 8.80 115.3H
4.08
400 7.96 6.22 57.7H 3.66
600 11.94 5.08 38.45H 3.43
800 15.92 4.40 29.5H 3.08
-
JUNE 2002 IEEE PESC-02 75
voltage
motor
+i -
i tot
compens
chock2%5
chock2%3chock2%1
+-
v
Voltage Measurement3
+-
v
V1
+-
v
V
T1
T
Source1
Source
Series RLC Branch3 Series RLC Branch2
Series RLC Branch1
Series RLC Branch
Scope4
Scope3
Scope2
Scope1
Scope
Ground (output)1
Ground (output)
Ground (input)8
Ground (input)5Ground (input)4
Ground (input)3 Ground (input)2
Ground (input)1
Ground (input)
Gnd
+i-
Current Measurement6
+i-
Current Measurement5+
i -Current Measurement4
+i-
Current Measurement3
+i -Current Measurement1
+i-
C
Bus Bar (horiz)7
Bus Bar (horiz)6
Bus Bar (horiz)5
Bus Bar (horiz)4
Bus Bar (horiz)3
Bus Bar (horiz)2
Bus Bar (horiz)1
Bus Bar (horiz)
AC Voltage Source
AC Current Source8
AC Current Source7
AC Current Source6
AC Current Source5
AC Current Source4
AC Current Source3
AC Current Source2
AC Current Source1
AC Current Source
50m cable 4x1
380kw/490rpm
200m cable 4x240
.
SIMULATED RESULTS USING
MATLAB/SIMULINK
-
JUNE 2002 IEEE PESC-02 76
SIMULINK RESULTS
-
JUNE 2002 IEEE PESC-02 77
SIMULINK RESULTS
-
JUNE 2002 IEEE PESC-02 78
ACTIVE FILTERING
Parallel type Series type
-
JUNE 2002 IEEE PESC-02 79
-2500
-1500
-500
500
1500
2500
0 5 10 15 20 25 30 35 40
I
[A]
Time [ms]
0
5
10
15
20
25
30
2 5 8 11 14 17 20 23
[% I1
]
Harmonics
-5000
-2500
0
2500
5000
0 10 20 30 40
Time [ms]
I D
yn
aco
mp
[A
]
0%
5%
10%
15%
20%
25%
30%
35%
2 5 8 11 14 17 20 23
Harmonics
[%I1
]
RESULTS OF ACTIVE FILTERING
Input current of a 6-pulse Rectifier driving a DC machine without any input filtering
Input current with Active Filtering
-
JUNE 2002 IEEE PESC-02 80
-1000
-500
0
500
1000
0 5 10 15 20 25 30 35 40
U [
V]
Time [ms]
0
2
4
6
8
10
12
14
2 5 8 11 14 17 20 23
[% U
1]
Harmonics
-1000
-500
0
500
1000
0 5 10 15 20 25 30 35 40
U [V
]
Time [ms]
0
2
4
6
8
10
12
14
2 5 8 11 14 17 20 23
[% U
]
Harmonics
Typical 6-pulse drive voltage waveform
Voltage source improvement with active filtering
-
JUNE 2002 IEEE PESC-02 81
SHUNT ACTIVE FILTERS
By inserting a parallel active filter in a non-linear load location we can inject a harmonic current component with the same amplitude as that of
the load in to the AC system.
C
FL
Equivalent circuit
-
JUNE 2002 IEEE PESC-02 82
Low implementation cost.
Do not create displacement power factor problems and utility loading.
Supply inductance LS, does not affect the harmonic compensation of parallel active filter system.
Simple control circuit.
Can damp harmonic propagation in a distribution feeder or between two distribution feeders.
Easy to connect in parallel a number of active filter modules in order to achieve higher power requirements.
Easy protection and inexpensive isolation switchgear.
Easy to be installed.
Provides immunity from ambient harmonic loads.
ADVANTAGES OF THE SHUNT OR PARALLEL
ACTIVE FILTER
-
JUNE 2002 IEEE PESC-02 83
WAVEFORMS OF THE PARALLEL ACTIVE
FILTER
Source voltage
Load current
Source current
A. F. output current
-
JUNE 2002 IEEE PESC-02 84
G1
ZZ
VI
G1
ZZ
ZI
LS
SLH
LS
LS
G1
ZZ
V
G1
1I
G1
ZZ
G1
Z
IL
S
SLH
LS
L
L
hSh
L ZG1
Z
LhC II
0Z
VG1IG1I
L
ShLHhSh
(53)
(54)
(55)
(56)
(57)
1Gh
0G1
LC GII (52)
If
Then the above equations become
PARALLEL ACTIVE FILTER EQUATIONS
-
JUNE 2002 IEEE PESC-02 85
L
ShLHhLh
Z
VII (58)
G1I
I
LH
S
LHI
LZ
G
= Source impedance
= Is the equivalent harmonic current source
= Equivalent load impedance
= equivalent transfer function of the active filter
For pure current source type of harmonic source SL ZZ
and consequently equations (53) and (55) become
SZ
(59)
1G1 h
(60)
Equation (55) is the required condition for the parallel A.F. to cancel
the load harmonic current. Only G can be predesign by the A.F. while
Zs and ZL are determined by the system.
Equation (59) shows that the compensation characteristics of the A.F. are not
influenced by the source impedance, Zs. This is a major advantage of the A.F.
with respect to the passive ones.
-
JUNE 2002 IEEE PESC-02 86
The DC bus nominal voltage, , must be greater than or equal to line voltage
peak in order to actively control
The selection of the interface inductance of the active filter is based on the
compromise of keeping the output current ripple of the inverter low and the same
time to be able to track the desired source current.
The required capacitor value is dictated by the maximum acceptable voltage
ripple. A good initial guess of C is:
Cmax
t
0 C
v
dtimax
C
dt
dimax
VV3
2
LL
ndC
F
dCV
.iC
n V= peak line-neutral voltage
dC V= DC voltage of the DC bus of the inverter
L i = Line phase current
Cmax v = maximum acceptable voltage ripple,
Ci = Phase current of the inverter
dCV
C
Also
-
JUNE 2002 IEEE PESC-02 87
For identifying the harmonic currents in general the method of computing
instantaneous active and reactive power is used.
Transformation of the three-phase voltages and and the three-
phase load currents and into - orthogonal coordinate.
w
v
u
v
v
v
2/3
2/1
2/3
2/1
0
1
3
2
v
v
Lw
Lv
Lu
L
L
i
i
i
2/3
2/1
2/3
2/1
0
1
3
2
i
i
, vu vv wv, iLv Lui Lwi
P-Q THEORY
-
JUNE 2002 IEEE PESC-02 88
Then according to theory, the instantaneous real power and the
instantaneous imaginary (reactive) power are calculated.
L
L
L
L
i
i
vv
vv
q
p
where
LLLL p~ppp
LLLL q~qqq
DC + low frequency comp. + high freq. comp.
DC + low frequency comp. + high freq. comp.
Lp
Lq
q-p
-
JUNE 2002 IEEE PESC-02 89
The conventional active power is corresponding to , the conventional reactive
power to and the negative sequence to the 2 f components of and .
The commands of the three-phase compensating currents injected by the
shunt active conditioner, , and are given by:
q
p
vv-
vv
2/3
2/3
0
2/1
2/1
1
3
2
i
i
i 1
Cw
Cv
Cu
Lp~
Lq~
Lp Lq
Cui Cvi Cwi
p
q
= Instantaneous real power command
= Instantaneous reactive power command
-
JUNE 2002 IEEE PESC-02 90
L
L
q~q
p~p
LL
L
q~qq
p~p
LL
LL
q~qq
p~pp
Current Harmonics compensation is achieved
Current Harmonics and low frequency variation
Components of reactive power compensation
Current Harmonics and low frequency variation
Components of active and reactive power compensation
Substituting
-
JUNE 2002 IEEE PESC-02 91
HARMONIC DETECTION METHODS
i) Load current detection iAF= iLh
It is suitable for shunt active filters which are installed near
one or more non-linear loads.
ii) Supply current detection iAF= KS iSh
Is the most basic harmonic detection method for series
active filters acting as a voltage source vAF.
iii) Voltage detection
It is suitable for shunt active filters which are used as
Unified Power Quality Conditioners. This type of Active
Filter is installed in primary power distribution systems. The
Unified Power Quality Conditioner consists of a series and a
shunt active filter.
-
JUNE 2002 IEEE PESC-02 92
SHUNT ACTIVE FILTER CONTROL
a) Shunt active filter control based on voltage detection
-
JUNE 2002 IEEE PESC-02 93
Using this technique the three-phase voltages, which are detected at the point of
installation, are transformed to and on the dq coordinates. Then two first
order high-pass filters of 5HZ in order to extract the ac components and
from and . Next the ac components are applied to the inverse dq
transformation circuit, so that the control circuit to provide the three-phase
harmonic voltages at the point of installation. Finally, amplifying each harmonic
voltage by a gain Kv produces each phase current reference.
dv~
qv~
dv qv
dv qv
hVAF vKi
The active filter behaves like a resistor 1/KV ohms to the external circuit for harmonic frequencies without altering the fundamental components.
The current control circuit compares the reference current with the actual
current of the active filter and amplifies the error by a gain KI . Each phase voltage detected at the point of installation, v is added to each magnified error
signal, thus constituting a feed forward compensation in order to improve current
controllability. As a result, the current controller yields three-phase voltage
references. Then, each reference voltage is compared with a high frequency
triangular waveform to generate the gate signals for the power semiconductor
devices.
AFi
AFi
iv
-
JUNE 2002 IEEE PESC-02 94
b) Reference current calculation scheme using source currents (is),
load currents (iL) and voltages at the point of installation (vS).
-
JUNE 2002 IEEE PESC-02 95
3- HYBRID ACTIVE-PASSIVE FILTER
Compensation of current harmonics and displacement power
factor can be achieved simultaneously.
-
JUNE 2002 IEEE PESC-02 96
In the current harmonic compensation mode, the active filter improves the
filtering characteristic of the passive filter by imposing a voltage harmonic
waveform at its terminals with an amplitude
ShCh KIV
-
JUNE 2002 IEEE PESC-02 97
THDi decreases if K increases.
The larger the voltage harmonics generated by the active filter a better filter
compensation is obtained.
A high value of the quality factor defines a large band width of the passive
filter, improving the compensation characteristics of the hybrid topology.
A low value of the quality factor and/or a large value in the tuned factor
increases the required voltage generated by the active filter necessary to
keep the same compensation effectiveness, which increases the active
filter rated power.
SF
F
Lh
Sh
ZZK
Z
I
I
1S
2h SF
FLh
iI
ZZK
ZI
THD
If the AC mains voltage is pure sinusoidal, then
-
JUNE 2002 IEEE PESC-02 98
Displacement power factor correction is achieved by controlling the voltage
drop across the passive filter capacitor.
TC VV
Displacement power factor control can be achieved since at fundamental
frequency the passive filter equivalent impedance is capacitive.
-
JUNE 2002 IEEE PESC-02 99
HYBRID ACTIVE-PASSIVE FILTER
Single-phase equivalent circuit Single-phase equivalent circuit
for 5th Harmonic
-
JUNE 2002 IEEE PESC-02 100
This active filter detects the 5th harmonic current component that flows
into the passive filter and amplifies it by a gain K in order to determine its
voltage reference which is given by
5FAF iKv
As a result, the active filter acts as a pure resistor of K ohms for the 5th
harmonic voltage and current. The impedance of the hybrid filter at the 5th
harmonic frequency, Z5 is given by
KrC5j
1L5jZ f
FF5
0K The active filter presents a negative resistance to the external Circuit, thus improving the Q of the filter.
FrK, 0V 5BUS 5S
T5S V
L5j
1I
-
JUNE 2002 IEEE PESC-02 101
CONTROL CIRCUIT
The control circuit consists of two parts; a circuit for extracting the
5th current harmonic component from the passive filter iF and a circuit
that adjusts automatically the gain K. The reference voltage for the
active filter 5FAF iKv
HARMONIC-EXTRACTING CIRCUIT
The extracting circuit detects the three-phase currents that flow into
the passive filter using the AC current transformers and then the -
coordinates are transformed to those on the d-g coordinates by
using a unit vector (cos5t, sin5t) with a rotating frequency of
five times as high as the line frequency.
-
JUNE 2002 IEEE PESC-02 102
SERIES ACTIVE FILTERS
By inserting a series Active Filter between the AC source and the load
where the harmonic source is existing we can force the source current to
become sinusoidal. The technique is based on a principle of harmonic
isolation by controlling the output voltage of the series active filter.
Equivalent Circuit
-
JUNE 2002 IEEE PESC-02 103
- The series active filter exhibits high impedance to harmonic current and consequently blocks harmonic current flow from the load to the source.
SC KGIA.F. theof tageOutput vol V
KGZZ
V
KGZZ
IZI
LS
S
LS
LLS
(61)
(62)
= Equivalent transfer function of the detection circuit of
harmonic current, including delay time of the control
circuit.
G
, 0G1
1Gh
(63)
-
JUNE 2002 IEEE PESC-02 104
K = A gain in pu ohms
The voltage distortion of the input AC source is much smaller
than the current distortion. ShV
If hLZK and hLS
ZZK
Then
ShLhLC VIZV
0IS
(64)
(65)
(66)
-
JUNE 2002 IEEE PESC-02 105
HYBRID SERIES AND SHUNT
ACTIVE FILTER
At the Point of Common Coupling provides:
Harmonic current isolation between the sub transmission and the
distribution system (shunt A.F)
Voltage regulation (series A.F)
Voltage flicker/imbalance compensation (series A.F)
-
JUNE 2002 IEEE PESC-02 106
SELECTION OF AF S FOR SPECIFIC APPLICATION CONSIDERATIONS AF Configuration with higher number of * is more preferred
Compensation for
Specific Application
Active Filters
Active
Series
Active
Shunt
Hybrid of
Active Series
and Passive
Shunt
Hybrid of
Active Shunt
and Active
Series
Current Harmonics ** *** *
Reactive Power *** ** *
Load Balancing *
Neutral Current ** *
Voltage Harmonics *** ** *
Voltage Regulation *** * ** *
Voltage Balancing *** ** *
Voltage Flicker ** *** *
Voltage Sag&Dips *** * ** *
-
JUNE 2002 IEEE PESC-02 107
CONCLUSIONS
Solid State Power Control results in harmonic pollution above the tolerable limits.
Harmonic Pollution increases industrial plant downtimes and power losses.
Harmonic measurements should be made in industrial power systems in order (a) aid in the design of capacitor or filter banks, (b) verify the design and installation of capacitor or filter banks, (c) verify compliance with utility harmonic distortion requirements, and (d) investigate suspected harmonic problems.
Computer software programs such as PSPICE and SIMULINK can be used in order to obtain the harmonic behavior of an industrial power plant.
The series LC passive filter with resonance frequency at 4.7 is the most popular filter.
The disadvantages of the the tuned LC filter is its dynamic response because it cannot predict the load requirements.
The most popular Active Filter is the parallel or shunt type.
Active Filter technology is slowly used in industrial plants with passive filters as a hybrid filter. These filters can be used locally at the inputs of different nonlinear loads.
Active Filter Technology is well developed and many manufactures are fabricating Active filters with large capacities.
A large number of Active Filters configurations are available to compensate harmonic current, reactive power, neutral current, unbalance current, and harmonics.
The active filters can predict the load requirements and consequently they exhibit very good dynamic response.
LC tuned filters can be used at PCC and the same time active filters can be used locally at the input of nonlinear loads.
-
JUNE 2002 IEEE PESC-02 108
REFERENCES
RECOMMENDED PRACTICES ON HARMONIC TREATMENT
[1] IEEE Std. 519-1992, IEEE Recommended Practices and Requirements for Harmonic Control in Electric Power Systems, 1993.
[2] IEC Sub-Committee 77B report, Compatibility Levels in Industrial Plants for Low Frequency Conducted Disturbances, 1990.
[3] IEC Sub-Committee 77A report, Disturbances Caused by Equipment Connected to the Public Low-Voltage Supply System Part 2 : Harmonics , 1990 (Revised Draft of IEC 555-2).
[4] UK Engineering Recommendation G.5/3: Limits for Harmonics in the UK Electricity Supply System, 1976.
[5] CIRGE WG 36.05 Report, Equipment producing harmonics and Conditions Governing their Connection to the Mains power Supply, Electra, No. 123, March 1989, pp. 20-37.
[6] Australian Standards AS-2279.1-1991, Disturbances in mains Supply Networks-Part 2: Limitation of Harmonics Caused by Industrial Equipment, 1991.
-
JUNE 2002 IEEE PESC-02 109
DEFINITIONS
[7] J. Arriilaga, D.A. Bradley, and P.S. Bodger, Power System
Harmonics,New York: Wiley, 1985.
[8] N. Shepherd and P. Zand, Energy flow and power factor in
nonsinusoidal circuits, Cambridge University Press, 1979.
EFFECTS OF HARMONICS
[9] J.M. Bowyer, Three-Part Harmony: System Interactions Leading
to a Divergent Resonant System, IEEE Trans. on Industry
Applications, Vol. 31, No. 6, Nov/Dec 1995, pp. 1341-1349.
[10] R.D. Hondenson and P.J. Rose, Harmonics: the Effects on power
Quality and Transformers, IEEE Trans. on Industry Applications,
Vol. 30, No.3, May/June 1994, pp. 528-532.
[11] J.S. Subjak and J. S. McQuilkin, Harmonics-Causes, effects,
Measurements and Analysis: An Update, IEEE Trans. on Industry
Applications, Vol. 26, No. 6, Nov/Dec 1990, pp. 103-1042.
[12] P.Y. Keskar, Specification of Variable Frequency Drive Systems
to Meet the New IEEE 51 Standard, IEEE Trans. on Industry
Applications, Vol.32, No.2, March/April 1996, pp. 393-402.
-
JUNE 2002 IEEE PESC-02 110
[13] T.S. Key, Cost and Benefits of Harmonic Current Reduction for
Switch-Mode Power Supplies in a Commercial Building, IEEE
Trans. on Industry Applications, Vol. 32, No. 5,
September/October 1996, pp. 1017-1025.
PASSIVE HARMONIC TREATMENT TECHNIQUES
[14] M.F. McGranaghan and D.R. Mueller, Designing Harmonic
Filters for Adjustable-Speed Drives to comply with IEEE-519
Harmonic limits, IEEE Trans. on Industry Applications, Vol. 35,
No 2, March/April 1999, pp. 312-18.
[15] F.Z. Peng, Harmonic Sources and filtering Approaches, IEEE
Industry Applications Magazine, July/August 2001, pp. 18-25.
[16] J.K. Phipps, A transfer Function Approach to Harmonic Filter
Design, IEEE Industry Applications Magazine March/April 1997.
[17] S.M. Peeran, Application, Design, and Specification of Harmonic
Filters for Variable frequency Drives, IEEE Trans. on Industry
Applications, Vol. 31, No. 4, July/August 1995, pp. 841-847.
-
JUNE 2002 IEEE PESC-02 111
[18] J. Lai and T.S. Key, Effectiveness of Harmonic Mitigation Equipment for Commercial Office Buildings, IEEE Trans. on Industry Applications, Vol. 33, No. 4, July/August 1997, pp. 1104-1110.
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