log approach for the high-precision track control of ships
TRANSCRIPT
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MARINE CONTROL
LOG approach for the high precision track control of
ships
T.
Holzhuter
Indexing terms: Track control, LQG-control, Kalman ilter
Abstract: Design ideas and experiences gained
during the development of an adaptive high
precision track controller for ships are
summarised. The controller is installed
on
a
number of different ships, using a variety of
position measurement systems. The design follows
the spirit of the LQG paradigm combined with a
model following feedforward strategy. The ship is
kept to a manoeuvring trajectory through a
combination of feedforward and LQG feedback
control. The variances and weighting coefficients
for the LQG controller are chosen systematically.
The large number of design parameters is reduced
by appropriate model scaling. In addition, a
decomposition structure of the Kalman filter is
exploited to reveal the important tuning
parameters.
1 Introduction
The development of a commercial track controller has
been refined over several years.
A
track controller for
special applications such as mine hunting and dredging
has been developed, using specialised position measure-
ment systems [l]. This is based on an adaptive course
controller
[2]. A
standard track controller for commer-
cial ships is now installed on a number of different
ships. Operating experiences with this controller have
been very satisfying, and are presented in detail in
[3].
The classical track control approach, which viewed
the track control loop as an additional feedback loop
around the course-keeping loop of the standard autopi-
lot, was felt to be inadequate when dealing with high
precision track control. The state space approach pro-
vides a more direct and lucid solution.
With the use of GPS as a standard position reference
system, a problem appeared, which seems to be typical
for the shipbuilding sector. Traditionally, GPS receiv-
ers and autopilots are manufactured by different firms
and thus only a narrow interface between the two
The filtering process is thus intermingled with the auto-
pilot, as the filtering should be based on an adequate
model of ship motion. This is not really surprising from
a theoretical point of view, although it is not reflected
by the industrial division of labour. The two communi-
ties should work more closely, and one aim of the
present work is to aid this communication process.
The proposed general controller design combines the
spirit of the LQG paradigm
[4]
with a model following
feedforward strategy. For track changes, a model based
manoeuvring trajectory is constructed,
on
which the
ship is retained by the track-keeping controller. This
feature allows smooth track changing manoeuvres and
can also be used to impose reliable predicted manoeu-
vring tracks on the radar screen.
The LQG feedback part of the track controller
involves a considerable number of tuning parameters.
This number may be reduced by the systematic use of
scaling and a simplification of the Kalman filter, which
also allows a more intuitive understanding of the
design choices involved.
c
Y
Fig.
1
Coordinate system for the description
o
ship motion
The angle 7p is the difference between actual heading and trac k course , U is the
forward velocity measured by the log,
v is
the cross velocity to starboard,
x
is
the position along the track, y is the cross-track-error
2 Ship
model
devices exists. Filtering of GPS data is crucial, how-
ever, when high accuracy is to be maintained during
track changing manoeuvres. Simple low pass filtering
of the individual position components is disastrous.
For a commercial
track
controller
the
amount of instal-
lation work has to be quite low,
so
the model must
have a small number of parameters, identifiable from
on-board measurements. The linearisation of the
EE,
1997
hydrodynamic equations of motion of a ship leads to a
IEE
Proceedings online no. 19971032
second-order model in the state variables: rate of turn
r
Pape r first received 3rd A pril an d in revised form 3rd October
1996
and sway velocity v See Fig.
1
and [ 5 ] . This model is
Th e a u t h o r i s wth Ha mb u rg Po l y t e c h n i c , Sa n d k a mp 13a, D-24259
often ill-conditioned with respect to identification when
Westensee , German y using on-board measurements [6]. The well-known
IEE
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Theory Appl., Vol. 144, No. 2, March 1997
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simplified model after Nomoto
[7]
seems preferable.
For the sway velocity, v = ar
is
assumed. The parame-
ters
K,
T of the simple linear model in eqn. 1 can be
roughly derived from general ship data.
2)
L
U
T=To -
K=K o -
U
L
The remaining states can be deduced from kinematic
relations according to Fig.
1.
2 =ucos$++sin$+d, 3 )
l =
usin$ + v
cos$ +
d,
(4)
The forward velocity of the ship is measured by the
speed log, and can thus be viewed as a known parame-
ter. The linearisation of this model is straightforward
and the fully linearised model is given in eqn. 5 .
f + \
0
0 0
0
0 0 0 0
+
T 0 1- 0 0 0 0 0 0 r
c
0
0
0 0
U?
0 0 0 0
5
= 0 0
0 -2Dh-wh
0 0 0 0
f
Y U
a 0 0 1 0 0 y
b 0 0 0 0
0
0 0 0 0
b
d?J 0 0
0 0 0
0 0 0 0 d ,
X 0
0
0 0 0
0 0 0 1
X
dz
0
0 0 0
0
0 0 0 0 d ,
0 0
0
0 0 0 0
0 0 0
0 0 0
0
o u
0 0 0
0 0 0 1
(5)
The model includes a coloured noise to model peri-
odic disturbances of the heading signal, due to coupled
roll and pitch motion in rough sea. The dominating
frequency of this disturbance model with states
(
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From the typical accuracies of position and heading
measurements, it is clear that the position measurement
does not contribute to an increase in the estimation
accuracy of the heading and turnrate. Estimation
of
the
states xk
k = 1,
..., 5 of the heading submodel should
therefore be independent of the position measurement
y,. This introduces further structural zeros into the
Kalman gain matrix, namely L , = 0. The result can
easily be checked numerically by letting R2 become
large compared to
R1,
while the ratios Q41R2and QslR2
remain constant. Taking L, = 0 leads to a suboptimal
filter, which in principle has
a
higher covariance
P
given by the Lyapunov equation
P = A(I LC)P(I LC)TAT+ ALRLTAT
+
BQBT
(9)
where A ,
B ,
C
are the state space matrices of the discre-
tised system. The increase of P over the optimal Po
provides a measure for the performance deterioration
due to the suboptimality. The actual increase in estima-
tion variances
of
less than 1% is negligible, as may be
seen from the Appendix by comparison of cases 1
and 2.
The decomposition of the heading and the track sub-
models can be driven even further. Setting
Lyw= 0
removes the direct influence of the heading innovation
on the position estimate. The gyro information still
finds its way to the position estimate in the next time
update, and so the deterioration of performance should
be small. The Appendix shows that the increase in esti-
mation variances due to this simplification is less than
10%. The increase is even less if the sampling time for
the gyro signal is shorter than that for the measure-
ment.
The above simplification treats the heading and turn-
rate estimates as a deterministic input to the track
model. The cross track channel, with the exception of
the deterministic input
Q
and i
=
/a,
orresponds to
the submodel of the forward channel, which is dis-
cussed in Section
4.
With these simplifications, the
three submodels are totally decoupled and each meas-
urement only affects the states of its respective sub-
model. The disturbances for the two position
measurements are assumed to be equal. For symmetry
reasons, the filter response and the gains for the two
track channels should also be equal. The suboptimal
Kalman gain matrix is
L =
The full submodel decomposition also proves advanta-
geous under limitations on software or cpu-time, as the
Kalman gains for the two track channels may be calcu-
lated analytically, as in Section 4.
The proposed approach reduces the number of
parameters to a set of five tuning knobs, which roughly
correspond to the following controller characteristics.
Typical values are also given, and justified later:
IEE Proc-Control Theory Appl. , Vol. 144,
No.
2, March
1997
Q 1 * l R ,
= lo4 Low pass for course filtering
Q2*lRW
lo3 Estimation time for the rudder bias
Q3/R, =
1
Intensity of wave filtering
QplRp
-
Low pass for position filtering
QdlRp
- Estimation time for the drift
Note that due to scaling, Q = Q I F and
Q;
=
Q2P. For the track-related variances, no scaling is
used because the dynamic changes with environmental
conditions and position fixing instrumentation, rather
than with the ship parameters. The choice of variances
for the two track submodels is discussed in Section 4.
The other variances determine the Kalman filter for the
heading submodel. As a consequence of submodel
decomposition, only the ratios QklR1k = 1, ..., 3 are
relevant. Selected frequency responses of the Kalman
filter for the heading submodel are shown in Fig. 2a.
This Kalman filter has two inputs, the measured head-
ing + and the rudder 6. The transfer function @/+, is
simply a low pass and the transfer function ?I+, is a
differentiator with low pass filtering.
C10
ISI
~o~
1ci2
1CT21/=oo
lo2
d2
loo lo2
f
requencywT, rad
a
b
t i me t l T
frequency w, radls
d
Fig.
2
ulmun filter f o r heading submodel
(a) Transfer functions @ &,',and I^*/I/I~
(b) Variation
of
transfer function
IQ,
with pi
E
{
lo6, O4 IO }
( c )
Speed of bias estimation
for Q, E {lo4,10 , O2}
(d) Intensity of wave filtering
Q, E (0,
0.2, I}, T
=
20
and
K
=
0.2
The variance ratio Ql/Rvcontrols the low pass filter-
ing of the heading signal. Fig. 2b shows the filtering for
different values of this parameter. Practical considera-
tions indicate that the time constant should roughly be
a factor of ten smaller than T, leading to a typical
choice of
Ql*lRv*
=
lo4.
The variance Q2 characterises the sensitivity to
changes of the rudder bias b; in traditional PID-con-
trol, this is chosen via the integral part. The frequency
response for this state is rather involved, as this esti-
mate depends
on
both inputs tp and 6. A choice of Q2
is made simply by looking at the time response of the
estimated rudder bias to a step in the true rudder bias.
A time constant of 3
5
T seems reasonable for this
estimation process
so
from Fig. 2c, a typical choice is
If Q 3 > 0, additional band pass filtering is intro-
duced. The necessary intensity of wave filtering changes
strongly with weather conditions. It is therefore advisa-
ble to estimate this variance online
[SI.
Fig.
2d
shows
the wave filtering effect for different values of Q3. The
e2 103.
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transfer function is given for an unscaled situation to
give a realistic impression of the involved frequency
range.
The full decomposition of the heading and track
model using the Kalman gains in eqn. 10 only has
an
obvious advantage if the online solution of the Riccati
equation poses a problem with respect to processor
time or software limitations. However, the decoupling
with L, (case 2 in the Appendix) is strongly advisable,
as
there is a serious performance deterioration problem
when the full Kalman gain matrix is used. In the latter
case, the measurement of the cross position component
regularly leads to
a
correction of the heading, rate of
turn and rudder bias. This influence
is
negligible if the
relative sizes of the noise variances R nd R2 are prop-
erly chosen and well behaved white noise disturbances
occur. If the position signal is corrupted with jumps,
then the corresponding large innovations lead to unac-
ceptable steps in the heading model states. This severe
performance problem is effectively solved by the gain
matrix structure with L, = 0.
4 Position filter
The estimation process
of
the three submodels for
heading, forward and cross position can be decom-
posed without significant error. The stochastic models
for the two track channels thus become identical. The
model for the forward channel y,
d,
is
Ym= ( 1 0 )
(y
(11)
The deterministic input, which is different for the two
channels, is omitted because it is not relevant to the
calculation of the gains. The Riccati equation for the
continuous system in eqn.
11
can be solved analytically,
and with Qp = Q4 = Q6 and Qd = Q5 = Q7, leads to
Kalman gains
Idy = I d s = l / Q d / R p
13)
It should be noted that the gains depend only on the
ratios QplRpand QdlR,. The transfer function for the
estimation of the drift IS
(14)
d , S
y m
-
+
( l y / l d y ) ~
+
(1 / l d y )S2
For d[Qd/Rp] 2 Q IRp the damping is Dp 1. In this
case, the sum of t t e two time constants serves
as
an
equivalent time constant
A
simple choice is
Qp = 0,
which assumes that all
deviations from the true position must be attributed to
the drift. However, this is not realistic because in the
cross track motion, for example, the errors in the
parameter
a
would then be interpreted
as a
drift. Some
choice Qp
>
0 has to be made.
If the ship
is
exposed to
a
step in the drift velocity,
the measured position ym shows a ramp increase. The
I24
drift is estimated from eqn. 14 by differentiation and
low pass filtering. See Fig.
3a.
The response of the
position estimate may be understood more clearly by
considering the transfer function
The response for a ramp increase is shown in Fig. 36.
The maximum estimation error decreases with
Zd y
Increasing
Qp
while leaving
Tdom
rom eqn. 15 constant,
leads to
a
decrease in
ldy
=
d[QdIRp].
hus the maxi-
mum estimation error is decreased. See Table 1 for
a
systematic variation. Considering typical rates of
change for the drift,
a
sensible choice is Tdo,= 100s.
F
.8
b
t i m e t , s
C
Fig. 3 Response of
position
Kalman j l t e r to
a
step in the drift
d,
f o r
dif
ferent
values
of Q
(a)
Estimated driftPJy,
(b) Error 2 of the estimated cross position
c) Response
of
position estimate
y^
to
a
step in the measured position
Table
1: Combinations
of
Qp
and
Q, for t h e e a s e s in
Fig.
3
Case Q Qd D a m p i n g
1 0
4 . 10-8 D, =
id2
2 8 .
O
1 .6 .
10-7
Dp=
1
3
1 10-2 1.2 . IO
D,
> 1
4
1 IO-' 1.1 .
10-5
D,>
1
Note tha t the var iance 0 i s a d ju s t e d t o g i ve r o u g h l y e q u a l
t im e r e sp o n ses
o f
the d r i f t es t im at ion see F ig .
3a)
If
Q,
is increased, the estimation of the position
becomes faster than the estimation of the drift. See Fig.
3b. This is desirable because the control loop also has a
drift compensation capability, which relies on the rec-
ognition of position errors. Fig.
3c
shows the estima-
tion error, which in turn results in
a
reduced track
error. However, the increase of
Qp
also increases the
sensitivity to the measurement noise of the position, so
that
a
medium value must be chosen,
as
in case 3.
The Kalman gains are calculated for the linearised
model. It is not advisable to use the linearised equa-
tions in the track extrapolation step (time update) of
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the online Kalman filter. For low speed and high cur-
rent, a considerable angle may be present between the
track course and the heading of the ship, leading to
noticeable estimation errors. A nonlinear extrapolation
step is therefore strongly recommended:
X:+l
=
f(kt)+BS
(17)
Xt+ = + L q -
CX,)
(18)
Here, 2* denotes the extrapolated state estimate,
while 2 is the state estimate after the measurement
update. The geometric nonlinearity of the system is
preserved in eqn. 17 of the Kalman filter by using a
discretised version of eqns. 3 and
4
in the nonlinear
function f x ) , instead of the linearised equations
according to eqn. 5 . This is just a simple case of the
extended Kalman filter technique.
5
LQG
contro l ler
The state space approach allows a straightforward
switching of control modes without distortions. The
Kalman filter can estimate the full state irrespective of
whether all the states are used for control. It should be
noted that the controllable part of the linearised model
is only of order
3
(+(d i j ) + i ) S 19)
The LQG controller minimises the stochastic per-
formance criterion, J
=
E xTWx
+ 8)
with x
= r ,
qj
y)*. The weighting of the rudder is chosen as unity,
without loss of generality since the optimisation only
depends on relative weightings. With diagonal weight-
ing matrices in the absence of specific information, the
criterion reduces to
J
=
E
(X,y2
+
+
X,T
+
S 2 )
(20)
The simplest choice would be A, = Ar =
0
for track
control, and Ay = kr =
0
for course control. This would
leave only one tuning parameter, which controls the
bandwidth of
the system. A slight modification is pro-
posed later.
If the weighting coefficients k are taken as fixed,
there is an undesirable variation of the closed loop
dynamics with the type of ship and its speed. This was
reported to produce difficulties in other applications of
LQG
control to ship steering [lo]. As discussed in Sec-
tion 2, the dependence on the individual ship may be
considerably reduced by scaling the model. The scaled
version of this model is given in eqn. 7. Rewriting the
performance criterion of eqn. 20 in scaled variables and
dividing the criterion by Kg2,eads to the scaled
weightings
A = X+ KT)2 (22)
A
= X,K 23)
Note that the scaling factors for Ay and kq are only
mildly speed-dependent, since according to eqn.
2,
U T
TJ
ToLand KT -
KoTo.
After scaling, the natural choice
is Ay*
=
1 for track control and AV
=
1 for course con-
trol.
A
mild variation in the interval
ky*
E
[0.1,
lo],
depending on the seastate, seems advisable. From the
intention of track keeping, i.e. minimising the variance
IEE Proc -Control T he ory A pp l , Vol 144, No 2, March 1997
of track deviations, the obvious choice is kq*
=
AT*=
0 .
However, the damping is improved by an additional
weighting of the heading; from Fig. 4a sensible choice
is kv* = loay*.
I
1
I I
0 100 200 300
time t s
Fig.
4 Response to unit step in the reference sign alfor dijj erent eightings
_ _ _ A;
= 0.
______ A y = 10h
*
In both cases A , =
1.
The track control
loop uses state feedback. I) track &ror, (ii) heading
In addition to the feedback gains, a disturbance com-
pensation using the estimated rudder bias and cross
drift must be applied. The compensating rudder for a
bias b is 6 = b /K. The stationary value of the rudder to
compensate a drift
dy
is zero. However, there has to be
an offset AQ in the set value of the heading
(24)
A+ = - arcsin-
U
For small relative drift values this can be linearised,
leading to a gain k dU in the drift, x7 = dy . The full
state feedback gain K is then
K =
( k q ,
k ,
O
0
k , O
0 )
( 2 5 )
To illustrate the control performance, Fig.
5
demon-
strates the transient behaviour for a step in the drift.
The maximum track deviation under this severe distur-
bance is less than 55m.
-8
i v)
0
100
200 300 LOO 500
ti me
t, s
Fig. 5
Controlperformance or a unit step in the drift
(i) Drift estimate
(0.1
i s ) ,
(ii) true position (IOm), (iii) position estimate (IOm),
(iv) heading
(0.1"),
(v) rudder (O.Io). Ship parameters:
K
= 0.2P1,T = 20s,
U
10m/s, Q = -50mirad
The sensitivity and complementary sensitivity func-
tions for the track control loop are shown in Fig. 6 for
different weighting coefficients Ay, which determine the
bandwidth of the controller. Although the plant has
two outputs, these transfer functions are scalar as there
is only one plant input. The norm 171wincreases with
bandwidth,
as
expected, indicating that the robustness
with respect to errors in the model parameters, e.g. the
rudder gain K, decreases. The norm of the minimal
destabilising multiplicative perturbation
lAlm
=
1/1
qW
decreases from
lAlm
= 0.72 for Ay =
0.1,
to
/AIm
= 0.62
for
Ay
= 1 0 .
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Fi .6 ensitivity function s S s) and complementary sensitivity functions
T(?j
of the LQG truck conrroL erfor d@ren t values
of
the weighting E
{ O . I , I , O}
LQG controllers do not provide guaranteed stability
margins, although the actual margins of the proposed
LQG controller are reasonable. The phase margin for
Ay = 1 is 6 = 56, and the gain margin is = 10. The
stability margins decrease with the degree of wave fil-
tering
as
this is a strongly model-dependent operation.
With Q3 = 1, the phase margin goes down to 6
=
40
and the gain margin to
E
=
2.9.
Some investigations
into the robustness properties with respect to errors in
the ship parameters have been presented in [111.
100
80
2 60
$ 40
.-
7J
2 o v
201
E 10
2
k o
L
V
-10
-201 , ,
,
, , , , , ,
b
L I
I
0
1000
2000 3000
4000
5
t ime , s
C
Fig. 7 Heading, track error and rudder angle during a typical voyage
a
Heading,
b
Track error, c Rudder angle
6 Operational experience
A
track controller designed according to the ideas
described in the previous Sections has been developed
and improved in recent years. The first application was
126
in the high-precision track control of mine hunters [l].
The intention was to apply the controller to commer-
cial ships as soon as a demand for track control arose
in this field. The controller was subsequently adapted
for use as a piece of standard equipment
on
commer-
cial ships. The controller is currently installed on a
number of different vessels, such as large ferries, differ-
ent types of cargo ships and special vessels with Voith-
Schneider propulsion. Several different position meas-
urement systems have been used, including differential
GPS,
which was used for the present results.
A general impression of the track-keeping quality
of
the system may be gained from Fig. 7.These data were
recorded on a voyage of the Norwegian ferry ship
Kong Harald. The track error during track-keeping
phases is below 5m, and the typical standard deviation
is 3m. During track changes, the track error is meas-
ured against the internally precomputed manoeuvring
trajectory. The error during these phases is typically
below 1Om. According to the navigation officers,
90%
of the voyages on the Kong Harald are performed in
track-keeping mode. The remaining 10% use course
control and hand steering mode. A detailed presenta-
tion
of
performance results can be found in
[3].
7 Conclusions
A systematic way to choose the considerable number of
design parameters for an LQG track controller has
been discussed here. Commercial track controllers
designed along these lines have been successfully
installed on a number of ships. Detailed performance
results have been presented in a recent paper [3]. Typi-
cally, the track errors achieved are well below 10m.
The approach presented uses a disturbance model
suitable for Kalman filter design. However, due to the
simplified model assumptions, the actual disturbance
variances are difficult to obtain. As an alternative, the
variances are used here as advanced tuning knobs
which reflect the specific disturbance structure of the
plant. The actual variances can thus be selected from a
general knowledge of the desirable observer response.
The described position filtering technique was origi-
nally designed for special navigation systems such as
Syledis or Doppler Sonar, and was later successfully
used with
GPS
receivers.
As
discussed in Section 1, the
position filtering and control process requires further
integration and this problem is addressed by the
present study.
If track errors are to be further decreased, a future
research problem is the robust estimation
of
sway
velocity during manoeuvres. In particular, an improved
capability to distinguish a stationary drift motion from
the transient, manoeuvre-induced sway motion would
be desirable.
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R.:
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1989, pp. 275-280
9
REID, R.E., TUGCU, A.K., and MEARS, B.C.: The
use
of
a
wave filter design in Kalman filter state estimation of the auto-
matic steering problem
of
a tanker in a seaway,
ZEEE
Trans.,AC-29,
(7), pp. 571-584
10
AMERONGEN,
J.:
Adaptive steering of ships model refer-
ence approach, Automatica, 1984,
20
(l ), pp. 3-14
11 HOLZHUTER, T.: On the robustness of course keeping autopi-
lots. Workshop on Artifical intelligence and a dvanced technology
in marine automation
CAMS 92, Genova, 1992, pp. 235-345
9 Appendix: Optimal and suboptimal Kalman
gains and their respective increases of variance
Ship parameters are K
=
0.2s-,
T
= 20s, U
=
10m/s, a
=
-50drad.
The relative increase is given by PkklPkko)
1.
Case 1:
Optimal Kalman filter with variance
Po
2.85
l o p 1
-2.35. lop5
9.58.
lo-
-1.36. l o p 5
-7.70.10 5.50. lo-
2.04. lo p2 4.85. lop4
1.22.10-6
2.65.
5.56.10-5
5.85.
/ O \
Case 2 : Suboptimal filter with
L, = 0
2.85
*
lo-
9.58. lo-
L =
( .33.lOW2
7.70. 10 5.50.
lo-
2.04. lo- 4.85. lop4
1.22 10-6
2.65.10-7
.67.10-3.56.10-5
1.60.10-3
1.31.10-4
2.57.10-4
diag(P)
=
P k k
= 6.32.
5.85.
lo-
pkkp l k ) =
Case 3 : Suboptimal filter with L, =
Lyw
= 0
[ 4.85.10-4.50 10-)
2.85
*
1 O - I 0
9.58
L = 3.33.10-
1.22 10-6
6.32.
l o p 7
2.65.10-7
.94.10-5
2.67.10-3
1.60.10-3
pkkp l k )
=
8.00.10-5
diag(P) = Pk,+=
6.09.
lo-
4.06 * lop2
.81 *
lo-
Case 4:
As
case 3, but with
Lyy
aken from the continu-
ous system approximation Ld = L, At according to Sec-
tion
4
L =
( )
2.8 5. 10-1 0
9.58.
lop2
5.48
*
5.00.10-4
1.22.10-6
diag(P) =
P k k
=
6.09.
5.95.10-5
2.67.10-3
1.60.10-3
p k k / p l k )
=
4.09. lop2
7.04. lo-
IEE Proc.-Control Theory Appl. , Vol. 144 No. 2, March 1997
127