model simpliflcation for auv pitch-axis control design · examine control design for pitch-axis...
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Model simplification for AUV pitch-axis control design∗
Jan Petrich Daniel J. Stilwell†
The Bradley Department of Electrical and Computer Engineering,
Virginia Polytechnic Institute & State University, Blacksburg, VA 24061
{jpetrich,stilwell}@vt.edu
Abstract
Although the use of low-order equivalent models is common and extensively studied for control of
aircraft systems, similar analysis has not been performed for submersible systems. Toward an
improved understanding of the utility of low-order equivalent models for submersible systems, we
examine control design for pitch-axis motion of an autonomous underwater vehicle (AUV). Derived
from first principles, the pitch-axis motion of a streamlined AUV is described by third-order dynamics.
However, second-order approximate models are common for system identification and control design.
In this work, we provide theoretical justification for both the use of and limitations of a second-order
model, and we verify our results in practice via a series of case studies. We conclude that a
second-order pitch-axis model should often be sufficient for system identification and control design.
Keywords: autonomous underwater vehicles, attitude control, linear equivalent model, stability
1 Introduction
Complete nonlinear AUV models of autonomous underwater vehicles (AUVs) are introduced in Fossen
[1994], Gertler and Hagen [1967] and Arafat et al. [2006]. In general, the parameters of those models are
obtained through tow-tank experiments as described in Hwang [2003], Barros et al. [2008], Prestero
[2001] and Williams et al. [2006], or by employing computational fluid dynamics (CFD) tools as
described in Humphreys [2001], Jenkins et al. [2003], Sahin et al. [1997] and Geisbert [2007]. However,
conducting time-consuming and expensive tow-tank experiments or CFD simulations is prohibitive for∗The authors gratefully acknowledge the support of the National Science Foundation via Grant IIS-0238092, and the Office
of Naval Research via Grant N00014-03-1-0444.†Corresponding author
1
AUVs whose payload configuration and hydrodynamic characteristics change frequently depending on
mission requirements. Examples of such modular AUVs that easily accommodate payload sensors are the
Ocean Explorer Smith et al. [1995], the Mares AUV Cruz and Matos [2008], and the Remus
AUV Moline and Blackwell [2005]. In our work, we justify simplifying assumptions regarding the highly
nonlinear AUV dynamics in theory and practice, and we investigate the utility of a low-order pitch-axis
model for in-flight system identification as proposed in Petrich et al. [2007] and subsequent model-based
attitude control design.
In steady-state flight at zero angle of attack, the linearized pitch-axis motion of a streamlined AUV, as
derived from first principles, reduces to third order. Linear third-order AUV pitch-axis models can be
found in Fossen [1994], Silvestre and Pascoal [1997], Vuilmet [2005] and Prestero [2001]. Nevertheless,
system identification and control design for streamlined autonomous underwater vehicles often assume a
second-order model for the pitch-axis motion, see for example Fossen [1994], Prestero [2001],
Cristi and Healey [1989], Li et al. [2004], Kim et al. [2001] and Cristi et al. [1990]. However, a rigorous
justification for second-order approximate models has not been previously addressed. For this reason, this
work attempts to establish theoretical justification for using a second-order pitch-axis model for
parameter identification and attitude control design of streamlined AUVs. In order to analyze why a
second-order approximation seems to work well in practice, we introduce an error model that defines a
useful relationship between the third-order model and a second-order approximation. We use the error
model to quantify neglected system dynamics and discuss stability and performance of the closed-loop
third-order model when using a controller that is designed based on a second-order approximation. Our
analysis and field trials show that a second-order pitch-axis model often suffices in practice for control
design.
The use of second-order models is also common in the aircraft community, where reduced-order
equivalent models have been extensively studied for evaluating flight performance, see for
example Mitchell and Hoh [1982] and Hodgkinson [1982]. No equivalent work has been done to address
the utility of low-order equivalent models for AUVs.
Limited sensing ability poses fundamental challenges for obtaining reliable model parameters from flight
data. In particular, smaller AUVs are often not instrumented to measure linear velocities, and thus the
angle of attack α is unknown. With the limited instrumentation in mind, we address identifiability of the
underlying physical parameters of AUV systems, such as lift and drag coefficients, within the scope of
linear dynamic model identification. We prove that physical AUV parameters are not uniquely
identifiable using in-flight system identification techniques, as presented in Petrich et al. [2007] for linear
models and in Smallwood and Whitcomb [2001] for nonlinear models, and therefore the parameters of the
identified model do not determine the physical parameters of the actual system. Thus, for the purpose of
identifying physical AUV parameters, a third-order model does not provide any advantages over a
second-order approximation. Without model parameters, a state observer that estimates α and thus
enables state feedback cannot be directly implemented. We deduce output-feedback gains from an
identifiable, second-order approximation of the plant, and we show that those feedback gains stabilize the
underlying third-order plant if the error model is sufficiently small. We formally quantify the relationship
between size of the error model and stability margins of the control system.
When designing AUV controllers, model parameters are commonly assumed to be known. For example,
linear third-order model parameters, determined experimentally through tow-tank experiments and CFD
simulations, are presented for the Remus AUV in Prestero [2001] or the MARIUS vehicle in Fryxell et al.
[1994]. In contrast, we identify linear pitch models in situ utilizing only instrumented variables onboard
the AUV. Our work is motivated by vehicle systems that change their external shape and/or mass
distribution (e.g., new external payload) frequently, and for which a revised control system is required. In
this case, control design is expedited if a dynamic model can be identified rapidly from AUV flight data.
Thus we address control design in the context of system identification and corresponding parameter
estimation errors. Similar work has been presented in Rentschler et al. [2006], in which the authors
identify the parameters of a canonical third-order AUV pitch-axis model using numerical minimization
tools under the assumption that the model is stable. While we do not impose a stability assumption, our
focus is on the relationship between the third-order model and a second-order approximation. We
presume that a stabilizing, although perhaps poorly performing, control systems is available for which in
situ flight data can be acquired and a model can be identified.
Experimental verification of our analysis is conducted using the Virginia Tech 475 AUV, shown in
Figure 1. The Virginia Tech 475 AUV is a conventional, streamlined vehicle that is nearly neutrally
buoyant, propelled at the stern, and controlled by movable control surfaces at the tail. It
weighs 8.5 kilograms and has a total length of 1 meter. The hull diameter is 0.12 meters (4.75 inches).
The Virginia Tech 475 AUV is capable of carrying various payload sensors needed for biological and
acoustic surveys, each of which changes the exterior shape and mass of the AUV. For this reason,
hydrodynamic properties such as lift and drag coefficients and added mass terms vary depending on the
payload. Thus, the ability to conduct in-flight system identification becomes particularly important. An
onboard attitude and heading reference system measures the vehicle’s pitch angle θ and pitch rate q. The
commanded elevator fin deflection used for attitude control is denoted δ.
Using three drastically different configurations of the Virginia Tech 475 AUV, we identify both
second-order and third-order linear pitch-axis models. We compare the resulting models and draw
Figure 1: Virginia Tech 475 AUV, named after its hull diameter of 4.75 inches.
conclusions about the performance and robustness of a control system that is designed based on a
second-order approximation. Comparing the full third-order dynamics to the second-order
approximation, we find a modest decrease in phase margin. We conclude that a linear second-order
pitch-axis model suffices for attitude control design of a slender and streamlined AUV.
This paper is organized as follows. In Section 2, we define linear third-order and second-order AUV
pitch-axis models. In Section 3, we introduce a model for the approximation error due to using a
second-order approximation for the third-order model. In Section 4, we investigate identifiability of the
underlying physical parameters (e.g., lift and drag) in the context of system identification. In Section 5,
we discuss inherent stability of the pitch-axis motion of a streamlined AUV, and in Section VI we
investigate control design. In Sections 7 and Section 8, we apply our results to the problems of system
identification and control design, respectively, for three configurations of the Virginia Tech 475 AUV.
2 Problem Statement
In this work we address the dynamics of a neutrally buoyant vehicle in level flight at zero angle of attack.
We assume a small separation between center of gravity and center of buoyancy, and a vehicle body with
three planes of symmetry. Under these assumptions, the linearized pitch dynamics are described by a
third-order model, see Fossen [1994], Prestero [2001] and Petrich et al. [2007]
α
q
θ
=
a22 a23 0
a32 a33 a34
0 1 0
α
q
θ
+
b21
b31
0
δ
y1
y2
=
0 1 0
0 0 1
α
q
θ
(1)
The states are angle of attack α, pitch rate q and pitch angle θ. The input is the elevator fin deflection δ.
As illustrated in Figure 2, the angle of attack α is defined between the body’s x-axis and the velocity
vector V , and the pitch angle is defined between the body’s x-axis and the XY -plane of the inertial
frame. Only pitch rate q and pitch angle θ are assumed to be instrumented, and thus the output signals
are y1 = q and y2 = θ.
α
V
q
θ
δ
xz
Y
X
Figure 2: A linear pitch-axis model describes the AUV motion in the body’s xz plane. Assuming constant
velocity V , the states are angle of attack α, pitch rate q, and pitch angle θ. The input is the elevator fin
deflection δ.
The model (1) is derived by restricting the motion of a rigid body in inviscid fluid to the xz-body plane
or dive plane, where x is the longitudinal axis and z is the vertical axis, and by linearizing the remaining
equations of motion around the steady-state flight condition. For the steady-state flight at zero angle of
attack, one can show that the vehicle’s speed V decouples completely from the remaining pitch motion.
Thus, we assume constant speed flight with V = V0. The coefficients of (1) are derived in Petrich et al.
[2007]
a32 =1Jy
V 20
{(mz −mx) +
12ρAbLCmα
}
a22 =1
2mzρV0Ab (CD0 + CLα)
a33 =1Jy
{12ρV 2
0 AbLCmq −mV0xcg
}
a23 =mx
mz
a34 = − 1Jy
zcgFw
b21 =1
2mzρV0AfCLδ
b31 =1
2JyρV 2
0 AfxfCLδ
(2)
The parameter Jy denotes the moment of inertia including added inertia along the pitch-axis. The AUV
parameters mx and mz represent the mass including added mass along x and z-axis, respectively. The
dry mass is m. The reference length is L and the location of the fins with respect to the center of
buoyancy is xf . The center of gravity is located at rcg =[xcg 0 zcg
]T. Hydrodynamic properties of
body and fins are characterized by the lift coefficients CLα and CLδand the corresponding reference
areas Ab and Af . The hydrodynamic coefficients Cmα < 0 and Cmq < 0 account for the body’s restoring
moment and viscous damping, respectively.
The transfer function corresponding to (1) isq(s)
θ(s)
=
s
1
β1s + β0
s3 + α2s2 + α1s + α0
δ(s)
=
s
1
G3(s) δ(s)
(3)
with the coefficientsβ1 = b31
β0 = a32b21 − b31a22
α2 = −a22 − a33
α1 = a22a33 − a34 − a23a32
α0 = a22a34
(4)
Although not fully justified, second-order pitch-models are found adequate for AUV control design in
practice, see for example Fossen [1994], Prestero [2001], Cristi and Healey [1989], Li et al. [2004],
Kim et al. [2001] and Cristi et al. [1990]. A typical second-order approximation isq
θ
=
A33 A34
1 0
q
θ
+
B31
0
δ (5)
with the corresponding transfer functionq(s)
θ(s)
=
s
1
B31
s2 −A33s−A34δ(s)
=
s
1
G0(s) δ(s)
(6)
In Fossen [1994], Prestero [2001] and Cristi et al. [1990], such a second-order model is derived by deleting
the state α in the third-order model (1), while in Cristi and Healey [1989], Li et al. [2004] and Kim et al.
[2001] it is proposed without justification.
In the sequel, we assume the existence of lumped parameters A33, A34, and B31 defining a second-order
model (5) that captures the dominating modes and approximates the input-output behavior of (1). In
Section 7, we verify this assumption in practice.
For aircraft, such as in Etkin [1959] or Stevens and Lewis [2003], pitch motion is characterized by four
states: speed V , angle of attack α, pitch rate q and pitch angle θ. Detailed analysis shows that even for
aircraft steady-state and level flight, the speed V does not decouple from the remaining states of the
linear system. Aircraft weight forces are not compensated for by buoyancy forces, as in the case of a
neutrally buoyant AUV, and a negative (positive) pitch angle accelerates (decelerates) the aircraft.
However, it is widely accepted that the fourth-order pitch dynamics are governed by two modes, namely
short period and phugoid mode. Due to the time scale separation of both modes, it suffices to examine
the second-order short period mode for attitude control, see Blakelock [1991] and McRuer et al. [1973].
3 Error Model
In this section, we address the approximation of the third-order plant (1) using a second-order model (5).
We define an error model between (1) and (5) which is used for stability analysis.
Applying standard system identification techniques, e.g. Ljung [1987] and Eykhoff [1974], the parameters
of G0(s) in (6) are determined by matching the input-output behavior of model and plant. Due to the
model approximation and truncation of system modes, we generally find A33 6= a33, A34 6= a34
and B31 6= b31, see Antoulas [2005]. Thus, the physical significance of the parameters A33, A34, and B31 is
not apparent.
We investigate the relationship between second-order approximation and third-order representation of the
plant through an error model. To derive an error model, we decompose the third-order transfer
function (3) as q(s)
θ(s)
=
s
1
G2(s) Ge(s) δ(s) (7)
The transfer function G2(s) contains the second-order approximation (6) augmented with the system
identification errors ∆A33, ∆A34 and ∆B31
G2(s) =B31 + ∆B31
s2 − (A33 + ∆A33) s− (A34 + ∆A34)
and Ge(s) represents an error model due to the truncation of a zero and a pole located at ze and pe,
respectively. That is
Ge(s) =s− ze
s− pe
The coefficients ∆A33, ∆A34 and ∆B31 can be interpreted as identification errors for natural frequency,
damping ratio and zero frequency gain of the second order system.
A qualitative pole-zero-plot of a third-order plant (black) and a second-order approximation (gray) is
shown in Figure 3.
The parameters A33, A34 and B31 from the second-order model (6) relate to the third-order model (7)
through the selection of a specific state space realization of (7). Such a state space realization contains
the states and parameters of the second-order approximation (6) as well as a generic, augmented third
state xα
xα
q
θ
=
pα aq aθ
cα A33 A34
0 1 0
xα
q
θ
+
bα
B31 + bq
0
δ
y1
y2
=
0 1 0
0 0 1
xα
q
θ
(8)
For any cα 6= 0, the coefficients in (8) and (7) satisfy the equalities
pα = pe + ∆A33
bq = ∆B31
cα bα = (B31 + ∆B31) (pe − ze + ∆A33)
cα aq = (A33 − pe) ∆A33 + ∆A34
cα aθ = ∆A33 A34 − pe ∆A34
(9)
−3 −2.5 −2 −1.5 −1 −0.5 0 0.5 1−1.5
−1
−0.5
0
0.5
1
1.5
Pole−Zero Map
Real Axis
Imag
inar
y A
xis
Figure 3: System Identification process: A linear second-order model (gray) is identified for an underlying
third-order plant (black).
Using the realization (8), the coefficients of the third-order transfer function G3(s) from (3) can be
expressed
β1 = B31 + bq
β0 = cαbα − pα (B31 + bq)
α2 = −A33 − pα
α1 = pαA33 −A34 − cαaq
α0 = pαA34 − cαaθ
(10)
Figure 4 contains a signal diagram of (8) showing the second-order approximation and peripheral,
structured uncertainties that define the error system.
Both state space models (1) and (8) are a realization of G3(s) in (3) and describe the same input-output
behavior. They are therefore equivalent under a state space transformation, but contain different
[A33 A341 0
]
[B310
][q
θ
]
1
s
δ
Second order
approximation
bα[aq aθ
]
[bq0
]
[cα0
]1
s− pα
Figure 4: Signal diagram of the second-order approximation and the peripheral error model.
parameter sets. In general, we find xα 6= α. Thus, we conclude that the parameters of the third-order
state space models (1) and (8) cannot be determined uniquely from the input-output behavior of the
plant. A rigorous analysis addressing the identifiability of the physical AUV parameters (2) is presented
in the next section.
4 Identifiability of Model Parameters
In this section, we investigate identifiability of the physical AUV parameters (2) given the available input
and output signals. Although, a canonical third-order model can always be identified, it cannot be used
to infer physical parameters of the underlying plant. Thus, we show that the state space
representation (1) is not uniquely identifiable from input-output data.
For the identifiability analysis, we rewrite (1)
x = A(p) x + B(p) δ
y = C x + D δ(11)
where the state vector is x =[α q θ
]T, the output vector is y =
[q θ
]Tand p is
p =[a22 a23 a32 a33 a34 b21 b31
]T∈ R7 (12)
a vector of parameters that contains the coefficients of (1). The parameterization of A(p) and B(p)
follows immediately from (1) with the matrix components defined in (2).
Identifiability is discussed in Grewal and Glover [1976] for a variety of systems. For our purposes, we
recall that the input-output behavior of a linear, time-invariant system is uniquely determined by the
Markov parameters gi. For the state space representation (11), the Markov parameters are given by
g0 = D
gi = C Ai−1(p) B(p) i = 1, 2 . . .(13)
and the Markov parameter matrix defined in Grewal and Glover [1976] is
G(p) =
D
C B(p)
C A(p) B(p)
C A2(p) B(p)...
C A2n−1(p) B(p)
∈ R2(2n+1) (14)
where n is the order of the system. For (11), n = 3. For the single-input system (11), the Markov
parameter matrix G(p) is a vector. The following theorem from Grewal and Glover [1976] states a
sufficient condition for local identifiability.
Theorem 4.1 The parameter vector p ∈ Rq is said to be locally identifiable at p ∈ Rq if
rank[
∂
∂pG(p)
]= q at p = p (15)
In other words, the Markov parameter matrix G(p) provides a local one-to-one map between system
parameters p and Markov parameters gi at p. Specifying Theorem 4.1 to the system at hand, we deduce
the following corollaries.
Corollary 4.2 Given the output signals y =[q θ
]Tfor system (1), the parameter vector p from (12) is
not identifiable.
Corollary 4.3 Suppose an augmented output signal y =[α q θ
]T, that is the output matrix of
system (1) satisfies C = I. Then, the parameter vector p from (12) is locally identifiable at every p, for
which poles and zeros of (1) do not coincide.
To prove Corollaries 4.2 and 4.3, we construct the Markov parameter matrix G(p) from (14) for each
case of C, and check the rank condition of the Jacobian matrix (15).
Corollaries 4.2 and 4.3 imply that identifying the parameter vector p requires that α is instrumented.
Therefore, deducing the physical AUV parameters (2) uniquely from the input-output behavior (1) is not
possible given the limited instrumentation of typical small AUV systems.
As compared to the seven parameters of (1), one can show that the five coefficients of transfer
function G3(s) in (3)
pc =[α0 α1 α2 β0 β1
]T∈ R5 (16)
are identifiable if the numerator and denominator polynomials in (3) do not share roots. In Section 7, we
estimate the coefficients pc and obtain a canonical third-order model G3(s) for the Virginia Tech 475
AUV.
5 Inherent Stability Assessment
In practice, linear second-order pitch-axis models are widely used for system identification and attitude
control design for AUVs. A common way to derive such a second-order model is to simply truncate α
in (1), see Fossen [1994], Prestero [2001] or Cristi et al. [1990]. For conventional vehicles, for which the
center of gravity is located below the center of buoyancy (zcg is positive), truncating α seems poorly
justified, because it always yields a stable system. In this section we show that fundamental system
properties such as stability need to be addressed more formally in the context of system simplification. In
particular, we examine the role of vehicle parameters in assessing stability of the third-order model (1),
and we demonstrate that stability assumptions about the second-order approximation do not imply
stability of the underlying third-order dynamics. For this reason, assuming a stable linear second-order
AUV pitch-axis model may not be feasible for system identification and control design.
We assess internal stability of the AUV’s pitch-axis model (1) by analyzing the coupling between α and
the remaining states q and θ. To expose these coupling terms, we propose a different representation of
the plant. We set δ = 0 and decompose the system (1) into two coupled subsystems
α(s) = Gα(s) q(s) and q(s) = Gq(s) a32 α(s)
with
Gα(s) =a23
s− a22and Gq(s) =
s
s2 − a33s− a34
(17)
Recalling q(s) = s θ(s), the transfer functions Gα(s) and Gq(s) originate from the first and second row
in (1), respectively. The overall internal system dynamics (1) are represented by the feedback system
shown in Figure 5.
Gq(s) Gα(s)αq
a32
+
Figure 5: Coupling between Gq(s) and Gα(s) through the parameter a32.
For a small horizontal separation xcg between center of gravity and center of buoyancy, we verify that the
poles of Gq(s) and Gα(s) remain in the open left half plane indicating stability of both subsystems. In
fact, the system parameters a33 and a34 in (2) suggest that Gq(s) resembles the motion of a physical
pendulum around the center of buoyancy. This motion is stable assuming both the existence of viscous
damping, modeled by a33 through the vehicle parameter Cmq < 0, and the location of the center of
gravity satisfying zcg > 0. Note that simply truncating α in (1) yields this stable pendular motion
q(s) = Gq(s) b31 δ(s)
The pole location of Gα(s) at a22 < 0 is characterized by the drag coefficient CD0 < 0 and the slope
CLα < 0 of the body’s lift coefficient, see (2).
We evaluate internal stability of (1) using the root locus of the series connection Gα(s) Gq(s) with respect
to the system parameter a32. Figure 6 shows a comparable numerical example of a root locus as function
of a32.
−3 −2.5 −2 −1.5 −1 −0.5 0 0.5 1−1.5
−1
−0.5
0
0.5
1
1.50.420.60.740.84
0.92
0.965
0.99
0.220.420.60.740.840.92
0.965
0.99
0.511.522.53
0.22
Root Locus
Real Axis
Imag
inar
y A
xis
a32 < 0
a32 > 0
a22 −
√
−a34
Figure 6: Root Locus representation of system poles as function of a32.
For a32 = 0, one recognizes the two complex poles of Gq(s) close to the imaginary axis and the single pole
of Gα(s) at a22. The parameter a32 is given in (2) and contains a destabilizing centripetal or munk
moment (mz −mx) V 20 > 0 and a restoring moment 1
2ρV 20 AbLCmα < 0 provided by the vehicle’s body.
Increasing a32 destabilizes the overall system by pushing two poles to the right half plane, while the pole
originally located at a22 moves further left. As illustrated in Figure 5, the parameter a32 acts as positive
feedback gain for the stable series connection Gα(s) Gq(s). Due to the proportionality between a32 and
V 20 , higher speeds are expected to increase the coupling.
We conclude that stability of both subsystems Gα(s) and Gq(s) does not imply stability of (1), and
simply truncating α may not preserve stability properties of the linear pitch-axis model. Thus,
second-order approximations, which are derived by deleting α, may not be reliable for system
identification and control design.
6 Control Design
In this section, we combine the results from previous sections to illustrate a control design approach that
utilizes the second-order approximation (6). We derive conditions under which output-feedback gains
derived from the second-order approximation ensure that the underlying third-order dynamics are
stabilized.
Referring to the state space representation (1), we distinguish between the AUV’s pitch motion defined
by the outputs q and θ and the AUV’s heave motion defined by the output α. It is well known that AUV
heave motion is non-minimum phase, see Narasimhan and Singh [2006] and Narasimhan et al. [2006], and
thus the corresponding transfer function contains a pole and/or a zero in the right half plane. However, a
similar statement about the pitch motion is not true in general.
Our control design strategy focuses on the case of stabilizing an unstable plant (7). The stability analysis
in Section 5, in particular the root locus approach in Figure 6, concludes that an unstable plant (7)
satisfies a32 > 0. With this assumption, it follows from (4) that
ze = −β0
β1= a22 − a32
b21
b31< 0
for a conventional vehicle with b31 < 0, b21 < 0 and a22 < 0. Thus, the zero ze of the transfer
functions (3) and (7) is located in the open left half plane.
For the control design process, we address output-feedback for the AUV pitch-axis models (6) and (7)
and select output-feedback gains Kp and Kd similar as in Prestero [2001]. However, for stability analysis,
we find it useful to suppose a single output θ(s). Then, the feedback gains Kp and Kd define a
PD-controller transfer function
Gc(s) = Kp + sKd (18)
recalling q(s) = s θ(s). We choose the feedback law (18) over a more general PID-framework that is
commonly used for AUV attitude control, see Fossen [1994], Petrich et al. [2007] or Rentschler et al.
[2006], because PD-control suffices to stabilize the second-order system. Integral control may be added to
meet performance criteria such as zero steady-state error, overshoot etc.
When selecting feedback gains for the second-order model G0(s) from (6), one commonly specifies the
natural frequency ω0 > 0 and the damping coefficient D > 0 for the closed-loop system
H2(s) =Gc(s) G0(s)
1 + Gc(s) G0(s)=
n2(s)d2(s)
Then, the denominator polynomial satisfies
d2(s) = s2 + (B31Kd −A33) s + B31Kp −A34
= s2 + 2Dω0s + ω20
and the nominal feedback gains are
Kp =1
B31
(A34 + ω2
0
)
Kd =1
B31(A33 + 2Dω0)
(19)
Since Kp and Kd are chosen exclusively based on a second-order approximation, nothing can be said
about whether or not the feedback law δ(s) = −Gc(s)θ(s) suffices to stabilize the third-order dynamics.
In the following, we augment the nominal feedback gains (19) such that closed-loop stability is
guaranteed for the underlying third-order plant (7). The third-order closed-loop system is
H3(s) =Gc(s) G2(s) Ge(s)
1 + Gc(s) G2(s) Ge(s)=
n3(s)d3(s)
(20)
The following proposition addresses the selection of such feedback gains.
Proposition 6.1 Suppose the second-order approximation satisfies |∆B31| < |B31| and assume that the
truncated mode is stable implying pe < 0. For the controller (18), let the feedback gains be
Kp =1
B31
(A34 + ω2
0 + γp
)
Kd =1
B31(A33 + 2Dω0 + γd)
(21)
with γp > 0, γd > 0 and suppose ω0 and D are selected to satisfy
D2 >1
4Ke
(1 +
2γp
ω20
)(22)
where
Ke = 1 +∆B31
B31∈ (0, 2)
Then, the closed-loop system (20) consisting of the third-order plant (7) and the controller (18) is
asymptotically stable if
−zeKeγp > |pe + 2ze| |A34|+ |pe + ze| |∆A34|
−zeKeγd > |pe + 2ze| |A33|+ |pe + ze| |∆A33|(23)
In other words, we increase robustness against parameter estimation errors and truncated pitch dynamics
by augmenting the nominal feedback gains (19) with sufficiently large, positive constants γp and γd.
Imposing the assumption |∆B31| < |B31|, we suppose that the sign of the input parameter B31 is
identified correctly. It is easy to verify that |∆B31| < |B31| implies
sign (B31) = sign (B31 + ∆B31)
Proof of Proposition 6.1: Using the assumptions ze < 0 and pe < 0, we divide the inequalities (23)
by −ze > 0 and note that
Ke γp > 2 |A34|+ |∆A34|
Ke γd > 2 |A33|+ |∆A33|
Using∣∣∣∣∆B31
B31
∣∣∣∣ < 1, we conclude
Ke γp >
∣∣∣∣∆B31
B31
∣∣∣∣ |A34|+ |∆A34|
Ke γd >
∣∣∣∣∆B31
B31
∣∣∣∣ |A33|+ |∆A33|
(24)
Similarly, we invoke 0 < Ke < 2 in (23), and find that
−zeKeγp > |pe + zeKe| |A34|+ |pe| |∆A34|
> |pe − zeKe| |A34|+ |pe| |∆A34|
−zeKeγd > |pe + zeKe| |A33|+ |pe| |∆A33|
> |pe − zeKe| |A33|+ |pe| |∆A33|
(25)
The denominator polynomial of the closed-loop transfer function H3(s) from (20) is
d3(s) = s3 + κ2s2 + κ1s + κ0
The coefficients κi, i = 0, 1, 2 are
κ2 = −pe − (A33 + ∆A33) + (B31 + ∆B31) Kd
κ1 = pe (A33 + ∆A33)− (A34 + ∆A34) + (B31 + ∆B31)Kp − ze (B31 + ∆B31) Kd
κ0 = pe (A34 + ∆A34)− ze (B31 + ∆B31) Kp
(26)
Referring to Routh’s Stability Criterion Routh [1930], all roots of the polynomial g(s) have negative real
part if and only if
κi > 0, i = 0, 1, 2 and κ2κ1 > κ0
Thus, we substitute Kp and Kd from (21) into (26) and check the signs of each coefficient κi individually.
For κ2, we find
κ2 = −pe − (A33 + ∆A33) + Ke (A33 + 2Dω0 + γd)
= −pe −∆A33 +∆B31
B31A33 + Ke (2Dω0 + γd)
Recalling the lower bound for Keγd from (24), we conclude
κ2 > −pe + Ke2Dω0 > 0 (27)
For κ1, we find
κ1 = pe (A33 + ∆A33)− (A34 + ∆A34) + Ke
(A34 + ω2
0 + γp
)− zeKe (A33 + 2Dω0 + γd)
= (pe − zeKe) A33 + pe∆A33 − zeKe (2Dω0 + γd) +∆B31
B31A34 −∆A34 + Ke
(ω2
0 + γp
)
With the lower bound for Keγp from (24), we simplify
κ1 > (pe − zeKe) A33 + pe∆A33 − zeKe (2Dω0 + γd) + Keω20
Invoking the lower bound for −zeKeγd from (25), we find
κ1 > −zeKe2Dω0 + ω20 > 0 (28)
For κ0, we find
κ0 = pe (A34 + ∆A34)− zeKe
(A34 + ω2
0 + γp
)
= (pe − ze) A34 + pe∆A34 − zeKe
(ω2
0 + γp
) (29)
Again, invoking the lower bound for −zeKeγp from (25), we conclude
κ0 > −zeKeω20 > 0
Finally, it remains to show that κ2κ1 > κ0. A lower bound for κ2κ1 is found by multiplying (27) and
(28), that is
κ2κ1 > (−pe + Ke2Dω0)(−zeKe2Dω0 + ω2
0
)
> −zeK2e (2Dω0)
2
Using the control design requirement (22), we rewrite the previous inequality as
κ2κ1 > −zeKe
(ω2
0 + 2γp
)(30)
We find an upper bound of κ0 by applying (25) to (29), that is
κ0 = (pe − ze) A34 + pe∆A34 − zeω20 − zeγp
< −zeKeω20 − zeKe2γp
(31)
Combining (30) and (31), we conclude
κ2κ1 > −zeKe
(ω2
0 + 2γp
)> κ0
Thus, all stability criteria are met.
¤
For control design purposes, Proposition 6.1 can be used to derive stabilizing output-feedback gains based
a second-order approximation (5). The assumptions in Proposition 6.1 include bounds on modeling errors
parameterized as coefficient errors ∆A33, ∆A34 and ∆B31, as well as signs of real-valued, truncated
zero ze and pole pe. Using an experimentally identified linear pitch-axis model for the Virginia Tech 475
AUV, we provide insight into the selection of γp and γd in Section 8.
7 Experimental Results, System Identification
In this section, we estimate the parameters of a linear second-order and third-order AUV pitch-axis
model using real data collected during field trials. The detailed parameter estimation process is presented
for the nominal configuration of the Virginia Tech 475 AUV shown in Figure 1. Comparing the identified
pitch-axis models for the Virginia Tech 475 AUV, we find that the difference between third-order model
and second-order approximation is marginal. In addition, we identify and compare third-order and
second-order models for two dramatically different payload configurations: the Virginia Tech 475 AUV
equipped with a forward-looking sonar, shown in Figure 7, and the Virginia Tech 475 AUV equipped
with a towed-hydrophone array, shown in Figure 8. All field trials are conducted at a constant propeller
rate of 2400 rpm which corresponds to a speed of approximately 1 ms−1.
We presume the closed loop system illustrated in Figure 9 in order to identify the parameters of a generic
pitch model Σ. The controller transfer function K(s) and the commanded pitch angle θr(t) are known,
Figure 7: Virginia Tech 475 AUV with an attached Forard Looking Sonar (AUV/FLS configuration).
Figure 8: Virginia Tech 475 AUV with an attached towed sensor array (AUV/TSA configuration).
and the collected data set contains the AUV’s trajectory θ(t), q(t) and δ(t). We simulate the trajectories
for pitch angle θ(t), pitch rate q(t), and elevator fin deflection δ(t) using the closed loop system from
Figure 9. The notation θ, q, δ distinguishes the simulated trajectories from the real trajectories θ, q, δ.
Applying a Nelder-Mead Simplex Method Lagarias et al. [1998], we estimate the parameters of the linear
pitch modelΣ
− controllerK(s)
−
δ
q
θ
θr
Figure 9: Closed loop system consisting of pitch model Σ that is second or third order, a controller transfer
function K(s) and a known commanded pitch angle θr.
pitch model Σ (second or third order) by numerically minimizing the cost function
J = θrms + τ qrms + δrms (32)
The root-mean-square error qrms is multiplied by τ = 1 second to obtain compatible units. The individual
root-mean-square errors are
ηrms =
√1T
∫ T
0‖η(t)− η(t)‖2 dt , η = θ, q, δ (33)
For the data set in Figure 10, T = 180 seconds.
Case 1: Using a second-order model (5) for Σ. The numerical minimization yields J = 3.70 deg, and the
parameter estimates are
A34 = −0.27, A33 = −0.91 and B31 = −1.84 (34)
Thus, the second-order model (5) is
˙q˙θ
=
−0.91 −0.27
1 0
q
θ
+
−1.84
0
δ (35)
The associated transfer function G0(s) from (6) is
G0(s) =θ(s)
δ(s)=
−1.84s2 + 0.91s + 0.27
(36)
Using the second-order model (35), the real and simulated trajectories are plotted in Figure 10 in gray
and black, respectively. Figure 10 shows pitch angle θ(t), θ(t) in the top plot and elevator fin deflection
δ(t), δ(t) in the bottom plot.
−10
0
10
θin
deg
0 20 40 60 80 100 120 140 160 180
−10
0
10
δin
deg
time in sec
Figure 10: Real (gray) versus simulated (black) AUV trajectories using a second-order model. Top: pitch
angle θ(t), θ(t), and bottom: elevator fin deflection δ(t), δ(t).
Case 2: Using a third-order model (8) for Σ. For a canonical third-order realization, the numerical
minimization yields J = 2.97 deg. The associated transfer function G3(s) from (3), containing the
coefficients pc, is
G3(s) =θ(s)
δ(s)=
−1.35s− 2.77s3 + 2.30s2 + 1.74s + 0.35
(37)
The parameters in model (8) are deduced by fixing the parameters A33, A34 and B31 from (34) and by
incorporating the canonical coefficients pc into the parameter identities (10). Setting cα = 1, the
parameter estimates are
pα = −1.39, aq = −0.21, aθ = 0.03, bα = −0.89 and bδ = 0.49 (38)
Thus, the state space model (8) is given by
˙xα
˙q˙θ
=
−1.39 −0.21 0.03
1 −0.91 −0.27
0 1 0
xα
q
θ
+
−0.89
−1.35
0
δ (39)
Using the third-order model (39), the real and simulated trajectories are plotted in Figure 11 in gray and
black, respectively. Figure 11 shows pitch angle θ(t), θ(t) in the top plot and elevator fin deflection
δ(t), δ(t) in the bottom plot.
−10
0
10
θin
deg
0 20 40 60 80 100 120 140 160 180
−10
0
10
δin
deg
time in sec
Figure 11: Real (gray) versus simulated (black) AUV trajectories using a third-order model. Top: pitch
angle θ(t), θ(t), and bottom: elevator fin deflection δ(t), δ(t).
Figure 10 and Figure 11 show that the simulated AUV trajectories are hardly distinguishable between
using the second-order model (35) and using the third-order model (39). For reasons of comparison, we
summarize the individual root-mean-square errors (33) in Table 1. We infer that the numerical fit in the
time domain barely improves when using a third-order model.
Table 1: System identification RMS errors (33) for θ, q and δ.
second-order model third-order model
θrms in deg 1.4172 0.9268
qrms in deg s−1 0.8977 0.8029
δrms in deg 1.3857 1.2404
J in deg 3.7006 2.9701
The bode plots and pole-zero plots for the second-order transfer function (36) and the third-order
transfer function (37) are shown in Figure 12 in gray and black, respectively.
In the frequency domain, we find in a qualitative sense that a second-order approximation captures the
dominating system dynamics with sufficient accuracy, see Figure 12. Although, the third-order model
contains an additional pole-zero pair (pe, ze), the additional mode does not have a significant impact on
the input-output behavior of the plant.
In order to quantify the difference between any two transfer functions P1(jω) and P2(jω), we adopt
an L2-error metric
∆ (P1, P2) = ‖P1 − P2‖L2
=1π
∫ ∞
0|P1(jω)− P2(jω)|2 dω
(40)
For the linear AUV pitch-axis models (36) and (37), we find ‖G0(s)‖L2 = 2.62, ‖G3(s)‖L2 = 2.68
and ∆(G0, G3) = 0.4244.
In addition to the nominal AUV configuration, we conduct system identification trials using the
AUV/FLS configuration from Figure 7 and the AUV/TSA configuration from Figure 8. For the
AUV/FLS configuration, the cost function J from (32) decreases from 4.90 deg when using a second-order
model to 4.83 deg when using a third-order model. For the AUV/TSA configuration, the cost function J
from (32) decreases from 2.50 deg when using a second-order model to 2.37 deg when using a third-order
model. Thus, for both AUV/payload configurations the improvement in predicting the AUV’s trajectory
using a third-order model instead of a second-order model is marginal in the time domain. To evaluate
the results in the frequency domain, we show the bode plots of estimated second-order and third-order
models including the associated L2 error metric ∆ in Figure 13 for the AUV/FLS configuration and in
Figure 14 for the AUV/TSA configuration.
−10
0
10
20
magnit
ude
indB
10−2
10−1
100
0
45
90
135
180
phase
indeg
Hz
−3 −2.5 −2 −1.5 −1 −0.5 0
−0.6
−0.4
−0.2
0
0.2
0.4
0.6
imagin
ary
axis
real axis
Figure 12: Nominal vehicle configuration: Bode plots (upper plots) and pole/zero locations (lower plot) of
the second-order pitch model (35) in gray and the third-order pitch model (39) in black. ∆ = 0.42.
−20
0
20
40
magnit
ude
indB
10−2
10−1
100
0
45
90
135
180
phase
indeg
Hz
−3 −2.5 −2 −1.5 −1 −0.5 0
−0.6
−0.4
−0.2
0
0.2
0.4
0.6
imagin
ary
axis
real axis
Figure 13: Forward Looking Sonar (FLS) vehicle configuration: Bode plots (upper plots) and pole/zero
locations (lower plot) of the second-order pitch model (35) in gray and the third-order pitch model (39) in
black. ∆ = 2.34.
8 Experimental Results, Control Design
In this section, we investigate whether the second-order model (35) suffices for designing a controller that
guarantees stability for the underlying third-order dynamics (39). For this reason, we first design a
−20
0
20
40
magnit
ude
indB
10−2
10−1
100
0
45
90
135
180
phase
indeg
Hz
−3 −2.5 −2 −1.5 −1 −0.5 0
−0.6
−0.4
−0.2
0
0.2
0.4
0.6
imagin
ary
axis
real axis
Figure 14: Towed sensor array (AUV/TSA) vehicle configuration: Bode plots (upper plots) and pole/zero
locations (lower plot) of the second-order pitch model (35) in gray and the third-order pitch model (39) in
black. ∆ = 0.23.
nominal feedback controller (19) based on the second-order model. Using the parameter estimates
obtained in Section 7, we explicitly compute an error model between (8) and (5), and design a second
feedback controller (21) using Proposition 6.1. Tracking performance and overall robustness are evaluated
for both cases.
For the nominal control design (19), we choose
ω0 = 2πf0, f0 = 0.5Hz and D =1√2
and obtain the nominal feedback gains
K(1)p = −5.22 and K
(1)d = −1.91 (41)
In addition to the nominal controller, we invoke Proposition 6.1 and compute additive feedback gains γp
and γd, which provide robustness against model uncertainties caused by truncated system dynamics and
system identification errors. For this reason, the third-order model (7) is populated using the estimated
parameters of (39) and the parameter equalities (9). The parameters of the error model (42) are
∆A34 = −0.88, ∆A33 = −1.09, ∆B31 = 0.49, pe = −0.30 and ze = −2.05 (42)
Invoking Proposition 6.1, we find γp = 2.17 and γd = 4.37, and the feedback gains (21) become
K(2)p = −6.40 and K
(2)d = −4.28 (43)
The superscripts (1) and (2) denote the nominal control design approach (19) and the robust control
design approach (21), respectively.
Recalling the controller’s transfer function Gc(s) from (18), we plot the open-loop transfer functions in
Figure 15. We use the second-order model G0(s) from (36) and show the bode plots of Gc(s)G0(s) in
gray, solid for the nominal feedback gains (41) and dashed for the robust feedback gains (43). Similarly,
we use the third-order model G3(s) from (37) and show the bode plots of Gc(s)G3(s) in black, solid for
the nominal feedback gains (41) and dashed for the robust feedback gains (43). For all four cases, phase
margins ϕm and required actuator bandwidth fa are summarized in Table 2. The gain margins are
infinite.
For the Virginia Tech 475 AUV, the parameter estimation in Section 7 reveals only a small difference
between the linear third-order pitch-axis model and the second-order approximation, see Figure 12. For
this reason, the respective open-loop transfer functions coincide well. In fact, the nominal feedback
gains (41), chosen based on a second-order model (35), already stabilize the underlying third-order
dynamics for the particular error model parameters (42). Only the phase margin reduces by 10 deg.
From Proposition 6.1 follows that the feedback gains (43) stabilize the underlying third-order system (7)
for all |∆A34| ≤ 0.88, |∆A33| ≤ 1.09 and |∆B31| ≤ 0.49. Thus, the feedback gains (43) increase robustness
−10
0
10
20
30
40m
agnitude
indB
10−2
10−1
100
101
−180
−135
−90
−45
0
f in Hz
phase
indeg
Figure 15: Open-loop transfer functions using second-order model (gray) and third order model (black).
The bode plots are shown for using nominal feedback gains (41) (solid) and robust feedback
gains (43) (dashed).
as compared to the nominal feedback gains (43). We find increased phase margins ϕm visible in Figure 15
and listed in Table 2. However, the required actuator bandwidth fa increases as a trade-off between
robustness and actuator effort is inevitable.
In order to evaluate the tracking performance, we plot the sensitivity transfer function for all four cases
in Figure 16. We show the bode plots of (1 + Gc(s)G0(s))−1 in gray, solid for the nominal feedback
gains (41) and dashed for the robust feedback gains (43). Similarly, we plot (1 + Gc(s)G3(s))−1 in black,
solid for the nominal feedback gains (41) and dashed for the robust feedback gains (43). Good tracking
performance is indicated by small sensitivity magnitude. In Figure 16, no significant difference is visible
between using a third-order model (black) and a second-order approximation (gray). However, we find
better tracking when using the robust controller (dashed) from (43) as compared to using the nominal
Table 2: Following Figure 15: phase margins ϕm and actuator bandwidths fa.
second-order model third-order model
nominal
gains (41)
(solid gray)
ϕm = 69.3 deg
fa = 0.66 Hz
(solid black)
ϕm = 58.9 deg
fa = 0.56 Hz
robust
gains (43)
(dashed gray)
ϕm = 85.9 deg
fa = 1.27 Hz
(dashed black)
ϕm = 79.2 deg
fa = 0.97 Hz
controller (solid) from (41). This is expected since we have increased actuator bandwidth in order to
attain increased robustness.
9 Conclusions
In this paper, we establish theoretical and practical justification for using linear second-order AUV
pitch-axis models for system identification and attitude control design. Our analysis rests on deriving an
error model which defines parameter correlations between the true third-order model and the
second-order approximation. We are motivated by severe size and weight constraints of miniature AUVs
that only allow for limited onboard instrumentation. In particular, we assume that the angle of attack α
is not known.
We prove that the physical parameters of a linear third-order model are not identifiable without
measuring α. Thus, we show that vehicle parameters such as hydrodynamic coefficients or added mass
terms cannot be obtained using online system identification.
We investigate stability of a streamlined AUV and show that truncating the state α always yields a
stable second-order model. However, rigorous stability analysis shows that the underlying third-order
dynamics may very well be unstable. Thus naive truncation of a state may yield incorrect results.
Field trials are an important component of our work. We use standard system identification techniques
to identify the parameters of a second-order pitch-axis model as well as the coefficients of a canonical
third-order realization for three different AUV configurations, and we show that a third-order model
yields negligible improvement over a second-order approximation in predicting pitch-axis motion.
−30
−20
−10
0
10 m
agnit
ude
indB
10−2
10−1
100
101
0
30
60
90
120
f in Hz
phase
indeg
Figure 16: Sensitivity transfer function using second-order model (gray) and third order model (black).
The bode plots are shown for using nominal feedback gains (41) (solid) and robust feedback gains (43)
(dashed).
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