modeling of antennas for thz radiation detectors · 2011-04-12 · em modelling (quickwave 3d ......
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Modeling of antennas for THz
radiation detectors
P. Kopyt, W. K. Gwarek
Institute of Radioelectronics
Warsaw University of Technology
Experiment 1 aiming at verifying whether FET detection was sensitive to the
polarization of the incident radiation: a commercially available GaAs/AlGaAs
FET was subject to linearly polarized 100 GHz radiation.
EM modelling (QuickWave 3D) allowed revealing the role of length and
orientation of bonding wires in defining the spatial orientation of the two-lobe
pattern.
a) Device sensitivity measured for 2 values of UGS
b) Far field simulations of the device with bonds
for properly adjusted impedances ZGS, and ZDG.
1 M. Sakowicz, J. Łusakowski, K. Karpierz, M. Grynberg, W. Knap, W. Gwarek, “Polarization sensitive detection of 100 GHz radiation by high mobility field-effect transistors”, JOURNAL OF APPLIED PHYSICS 104, 024519 (2008)
Motivation
100 GHz
radiation
Antenna is a device which should
effectively couple the EM plane
wave propagating in free space to
a lumped element, eg. input impedance Z0 of a receiver.
E-field component (in space)
Z0
A load – lumped
impedance
EM plane wave
Intermediary
element
Antennas
Antenna realizations
Wideband horns
Dielectric resonator antennas
Open quad ridge horns
Antenna parameters 1
Directivity D(θ,φ) of an antenna measures
the ability of the antenna to direct its power
towards a given direction
Radiation intensity U(θ,φ) is the power radiated by an antenna with the P per
unit solid angle.
Radiated power density Pr total power emitted by an antenna per unit area
rE
1∝
rH
1, ∝
UI – same power but radiated
isotropically
U(θ,φ)
UI
Antenna parameters 2
Efficiency ηηηη defines all loss mechanisms (e.g. ohmic losses of the currents flowing on the antenna wires or volumetric losses in the dielectric)
Gain G(θ,φ) also measures the ability of the antenna to direct its power towards
a given direction, however the normalization is to power delivered to the
antenna terminals.
ηηηη
For a lossless antenna the efficiency factor will be unity. In the case, there is
no distinction between directive and power gain. In real cases ηηηη < 1 (not all delivered power is radiated)!
ηηηη PT Prad
Power lost to heat in
metal and dielectric
Energy stored in
antenna volume
PRPrad
Power lost to heat in
metal and dielectric
Energy stored in
antenna volume
Antenna parameters 3
Effective area A describes the ability of an antenna to extract power from an
incident EM wave.
Diameter(m)
A(m2)
ApertureSize (m2)
Apertureefficiency
0.30
0.45
0.60
0.90
1.20
1.80
0.0375
0.0802
0.1494
0.3121
0.6828
1.3624
0.0707
0.1590
0.2827
0.6362
1.1310
2.5447
0.53
0.50
0.53
0.49
0.60
0.53
The effective area (A) is not equal to the physical
area of an antenna! A is typically a fraction of the
physical area (55–65% for dishes and 60–80% for
horns).
Antenna parameters 4
ZA
Input impedance ZA is the antena impedance as seen by a generator feeding
the antenna: ZA = RA + jXA.
where, PT,max and PR,max are available power from the generator or from the antenna respectively
Under impedance matching conditions:
Impedance matching affects the delivered power.
Antenna parameters 5
Bandwidth BW range of frequencies within which the performance of the
antenna, with respect to some characteristic, conforms to a specified
standards/requirements.
Impedance bandwidth BWZ range of frequencies within which the antena
reflection coefficient ΓΓΓΓ for its input remains low.
Radiation bandwidth BWR range of frequencies within which the antena
radiation characteristics stays within the desired limit. Typically BWZ < BWR
center
lowerupper
Zf
ffBW
−=
fupper flower
fcenter
Elevation [o]
Antenna analysis methods 1
Analytical methods typically possible for antennas of simple geometries, like
linear antennas, selected horn structures, open-ended waveguides used as
radiating structures.
Example: half-wavelength dipole :
Antenna analysis methods 2
Numerical methods employed complex radiating geometries based on the
Finite Difference Time Domain – FDTD (QuickWave 3D, CST); Finite Elements
Method – FEM (HFSS) or Method of Moments – MoM (Sonnet, FEKO).
FDTD method implemented in QuickWave 3D, QWED, Poland
Standard FDTD cells:
air dielectric metal
dielectric media interfaces
metal boundaries
Conformal cells in QuickWave 3D:
Classical examples of application 1
Axially symmetrical corrugated horn for satellite communication:
Hφ at 13.75GHz Design & measurements: P. Brachat, IEEE Trans. AP,
April 1994
6 GHz
-40
-30
-20
-10
020
40
60
80
100
120
140
160200
220
240
260
280
300
320
340
Pyramidal horn antenna for military surveillance:
Design & measurements:
Prof. B. Stec,
Technical Military Academy, Poland
------ vertical plane measured
____ vertical plane simulated
------ horizontal plane measured
____ horizontal plane simulated
Classical examples of application 2
Amplitude and phase imbalance
– from the measured (noisy)
and simulated (smooth) results.www.mma.nrao.edu/memos/html-memos/alma278/memo278.pdf
www.mma.nrao.edu/memos/html-memos/alma343/memo343.pdf
WR-10 waveguide quadrature hybrid1 with
six branch lines (S.Srikanth and A. R.
Kerr, National Radio Astronomy
Observatory, Charlottesville, VA 22903,
USA)
The radiation pattern
The dominating E-field
component magnitude (TM00)The impedance matching of the antenna
Numerical antenna analysis
Patch antennas are mostly analysed numerically as analytical approach is
limited to very thin substrates, not applicable to proximity/apperture coupled
antennas.
Example: rectangular patch antenna for 340 GHz
Thickness of the substrate and planar antennas performance
Rectangular patch Circular patch
Impedance bandwidth BWZ
Thickness of the substrate and planar antennas performance 2
The fields distribution under the metalization layer
Instanteneous H-field distribution in the axial-
plane of antenna (f = 300 GHz)
d = 40 µm
(~λ/8)
d = 90 µm
d = 200 µm
Printed dipole on thick
silicon (εr = 11.65) substrate
The substrate supports propagating waveguide modes (simplified 1-D analysis):
• TMn (existence of transverse H-field components and longitudinal E-field in the substrate: Hx, Hz i Ey)
• TEn (existence of transverse E-field components and longitudinal H-field in the substrate : Ex, Ez i Hy).
14
,
−=
r
TETMn
d
ncf
ε, where n = 0, 1, 2, 3, ...;The cut-off frequency is defined as:
Thickness of the substrate and planar antennas performance 3
The cut-off frequency of substrate modes
vs. substrate thickness
Propagation const.
Im γ for TM0
Propagation const.
Im γ for TE1
Thickness of the substrate and planar antennas performance 4
A numerical experiment to further investigate
substrate supports propagating waveguide modes (this time 3-D numerical analysis):
• change silicon substrate thickness
• measure the radiated power (into air)
• Compare the value with the power delivered to the antenna
An antenna on thick substrate with a box necessary to calculate power radiated into air
air region
How much power propagates in substrate and never get out into air?How much power in each substrate mode?
Thickness of the substrate and planar antennas performance 5
The effect employed in Dielectric Resonator Antennas (DRA), where:
• The metal element on the substrate is no longer radiating, but used only to excite proper field distribution within the dielectric
• The dielectric slab of proper dimensions (3-dimensional – thick) radiates from its sides!
An example DRA1 excited through the apperture:
In practice, the substrate under the
printed dipole must end. For thick
substrates supporting propagating modes,
the side of the slab start to radiate. The metal element only excites the fields.
1 K. M. Luk, K. W. Leung, „Dielectric Resonators Antennas”, Research Studies Press, Ltd.
Reciprocity principle states that applying a voltage V to terminals of antenna A,
a current I is measured at the terminals of antenna B. The same current will be
measured at the teminals of antenna A if the voltage V is applied to antenna B.
For linear isotropic medium the reciprocity principle allows to investigate
radiating structures either as a receiving antenna coupling the external radiation
to the receiver or — by reciprocity — as an antenna radiating a particular
pattern when excited at its terminals. In both cases the antenna properties
including the radiation/reception patterns should be the same.
Reciprocity principle
Analysis a structure with applying excitation at the antenna terminals:
• Separate calculations of the antenna impedance ZA, and• The antenna gain G,
• Combining the above to obtain responsivity R of the analyzed structure.
V:
)Re()1(4
G 222
TRZR Γ−Π
∝λ
)Re(2, TRRba ZPUR =∝
Responsivity of the structure is proportional to Ua,b at the
load (transistor) terminals.
incR APP =max,
Maximum power delivered by the antenna depends on the
incident wave power Pinc and the effective area A of the
antenna.
Power actually delivered to the load depends on the
impedance matching between antenna and the load.)1(
2
max, Γ−= RR PP
Normalized responsivity of a structure
G, ZA
Excitation of the antenna terminals
Excitation of the antenna terminals 2
A bolometer detector 1-3 modelled using the approach with excitation of the
antenna terminals, obtaning the ZA and G.
The peak responsivity predicted numerically (498
GHz) lies close to the measured one (524 GHz).
hot electron bolometer, Rb = 75Ω
Twin-slot antenna on thick silicon
substrate (1.3 × 1.4 × 0.25 mm3)
1 R. A. Wyss, A. Neto, W. R. McGrath, B. Bumble, and H. LeDuc, “Submillimeter-wave spectral response of twin-
slot antennas coupled to hot electron bolometers,” in Proc. 11th Int. Space Terahertz Technology Symp., Ann
Arbor, MI, May 1–3, 2000, pp. 379–388.2 B. S. Karasik, M. C. Gaidis, W. R. McGrath, B. Bumble, H.G. LeDuc, “A low-noise 2.5 THz superconductive Nb
hot-electron mixer,” IEEE Trans. Appl. Supercond. 7 (2), 3580 (1997).3 B. S. Karasik, private e-mail communication, Nov 2010.
)Re()1(4
G 222
TRZR Γ−Π
∝λ
Analysis a structure using plane wave as an excitation :
• Generate a plane wave incident on a structure;• The structure is loaded with received/detector impedance;
• Observe voltage at the load (FFT necessary to get Uf ).
Responsivity of the structure is proportional to Ua,b at
the load (transistor) terminals.
Since Ua,b is given explicitely, no need to separately
analyze G and ZA.
The difficulty lies in proper definition of ZTR in the
full-wave simulation.
Excitation of antenna with plane wave 1
E-field magnitude in a silicon slab irradiated with planewave
The field distribution within the thick (125 µm) silicon substrate subjected to
THz irradiation (dimensions: 2.20 × 2.25 × 0.125 µm3).
250 GHz 300 GHz 350 GHz
E-field intensity recorded in the location of C14 transistor
Excitation of antenna with plane wave 2
The chip1 consisting of 61 detectors with bow-tie antennas that was subjected
to plane wave irradiation. A simplified version of the metalization planes was
prepared.
Excitation of the multiple detectors with plane wave 1
1 Montpellier university group.
The topology of the metallization planes (layers
shown with colors)
Simplified 1-layer topology with
dicretization
Excitation of the multiple detectors with plane wave 2
The plane wave irradiation revealed a sharp peak of voltage at the C14 antenna
load. Peeling the structure of unnecessary elements allows to point out those
responsible.
Normalized voltage at the C14 antenna load
The stripped-down
structure that still shows
the peak.
Conclusions
• Bonded structures subjected to THz irradiation have antennas (even if
uninteded ones). One needs to take them into account while analysing the behavious of analysed structure.
• The behaviour of planar antennas realized on thick substrates stop to
be governed by sizes of the metal elements (e.g. length of the dipole arms) – the substrate size and its properties start to play a role.
• The numerical analysis may help in understanding the behaviour of detectors integrated with antennas but…
• The more complex the structure the more difficult is its analysis as
multiple effects (e.g. thick substrate, multiple of metalic objects/tracks on the surface) add up like in the case of the 61-detector chip.
Questions ?