research article realization of svm algorithm for indirect ...research article realization of svm...

Research ArticleRealization of SVM Algorithm for Indirect Matrix Converter andIts Application in Power Factor Control

Gang Li

College of Instrumentation and Electrical Engineering, Jilin University, Changchun 130061, China

Correspondence should be addressed to Gang Li; [email protected]

Received 18 June 2015; Revised 14 August 2015; Accepted 26 August 2015

Academic Editor: Don Mahinda Vilathgamuwa

Copyright © 2015 Gang Li. This is an open access article distributed under the Creative Commons Attribution License, whichpermits unrestricted use, distribution, and reproduction in any medium, provided the original work is properly cited.

Compared with AC-DC-AC converter, matrix converter (MC) has several advantages for its bidirectional power flow, controllablepower factor, and the absence of large energy storage in dc-link. The topology of MC includes direct matrix converter (DMC)and indirect matrix converter (IMC). IMC has received great attention worldwide because of its easy implementation and safecommutation. Space vector PWM (SVM) algorithm for indirect matrix converter is realized on DSP and CPLD platform in thispaper. The control of the rectifier and inverter in IMC can be decoupled because of the intermediate dc-link. The space vectormodulation scheme for IMC is discussed and the PWM sequences for the rectifier and inverter are generated. And a two-stepcommutation of zero current switching (ZCS) in the rectifier is achieved. Input power factor of IMC can be changed by adjustingthe angle of the reference current vector. Experimental tests have been conducted on a RB-IGBT based indirect matrix converterprototype. The results verify the performance of the SVM algorithm and the ability of power factor correction.

1. Introduction

AC/AC conversion has two main types: AC-DC-AC con-verters and direct AC/AC converters. AC-DC-AC convertersinclude the current and voltage source topologies with acapacitor or inductor in the dc-link.DirectAC/ACconvertersinclude the cycloconverter of high-power applications andmatrix converters in low power range [1]. Matrix converterhas a compact structure without capacitor or inductor, whichhas received much attention in the academic and industrialfields worldwide in recent years [2–6]. Since Alesina andVenturini proposed a control method for matrix converterusing amathematical approach to generate the desired outputvoltage [7], the PWM algorithms for matrix convertersbecome a research focus. New PWM strategies for matrixconverters have been proposed in recent years [8–13]. Someresearcher concentrated on the realization of the PWMschemes, such as dipolar modulation technique [8], SHE-PWM [9], and beatless synchronous PWM [10]. The PWMstrategies for matrix converter are also proposed to reducethe ripple in the input and output waveforms [11, 12]. In thehigh-power applications, indirect SVPWM formultimodularmatrix converters is realized [13].

The topologies of matrix converter, including directmatrix converter and indirect matrix converter [14–16], areanother research focus inAC/ACconversion. Comparedwiththe former one, IMC has several advantages. (1) With a realdc-link, the converter consists of two stages, a rectifier and aninverter. The control of the two stages can be decoupled andthe control difficulty is lowered down. (2) With appropriatemodulation method, zero-current switching commutationin the rectifier can be simply accomplished. The systemefficiency is improved. (3) The number of power switchescan be further reduced. (4) With the dc-link, multioutputIMC can be realized [17, 18]. The topology of IMC is shownin Figure 1. The bidirectional switch in the rectifier stage iscomposed by two RB-IGBTs.

The PWM strategies in [7–13] are proposed for DMC.In [19–22], the conventional PWM algorithm, based on twolarger source line voltages, is proposed. The PWM periodof the rectifier stage is divided in two segments to reducethe switching times and the harmonics of the input current.But these PWM strategies have no zero vectors. In [23–26],carrier-PWM realization and overmodulation method forIMC are discussed.

Hindawi Publishing CorporationAdvances in Power ElectronicsVolume 2015, Article ID 740470, 10 pageshttp://dx.doi.org/10.1155/2015/740470

2 Advances in Power Electronics

Input filter Rectifier stage based onRB-IGBT

Clampcircuit

Inverter stage

A

C

B

a

b

c

p

n

M

Figure 1: Topology of indirect matrix converter using RB-IGBT.

Load

a

b

c

idc

Sa Sb Sc

ia

ib

ic

ub

ua

uc

Figure 2: Control principle of the rectifier.

In the applications of indirect matrix converter, [27]proposes IMC to control doubly fed induction generation forwind power system. IMC is used to control a microturbinegenerator [28]. A multimodular indirect matrix convertertopology is proposed to be a frequency converter used inthe medium-voltage motion drive systems [29]. And threelevel neutral-point-clamped indirect matrix converters areproposed in [30].

In this paper, the rectifier is controlled as a current-source converter and inverter is controlled as a voltage-sourceconverter. SVM is applied for the rectifier and SVPWM isapplied for the inverter. The PWM sequence for indirectmatrix converter is achieved. Two-step commutation of zero-current switching for the rectifier is presented. The principleof the input power factor correction for IMC is discussed.The design and implementation of indirect matrix converterprototype using RB-IGBT are introduced. The experimentalresults are shown to verify the performance of the proposedPWM algorithm and the ability of PFC.

2. Space Vector Modulation of IMC

2.1. PWM Algorithm of IMC. The control of the rectifier andinverter for IMC can be decoupled because of the dc-link.Therectifier is controlled as a current-source converter, and theinverter can be seen as an inductive load in dc-link, shown inFigure 2.

Three phase input currents can be defined as follows:

𝑖𝑗 = 𝑆𝑗 ⋅ 𝑖dc 𝑗 = 𝑎, 𝑏, 𝑐. (1)

In (1), 𝑆𝑗 is the switch function. 𝑆𝑗 can be 1, 0, and −1,which are shown in Figure 3. The switching functions of therectifier are shown in Table 1.

Current space vector can be defined as follows:

𝐼 = 𝑖𝑎 + 𝑖𝑏 ⋅ e𝑗2𝜋/3

+ 𝑖𝑐 ⋅ e−𝑗2𝜋/3

. (2)

From (1) and (2),

𝐼 = 𝑖dc (𝑆𝑎 + 𝑆𝑏 ⋅ e𝑗2𝜋/3

+ 𝑆𝑐 ⋅ e−𝑗2𝜋/3

) . (3)

Advances in Power Electronics 3

Sa

(a) 𝑆𝑎 = 1

Sa

(b) 𝑆𝑎 = −1

Sa Sa

(c) 𝑆𝑎 = 0

Figure 3: The statues of 𝑆𝑎.

Table 1: Switching functions of the rectifier.

Number 𝑆𝑎 𝑆𝑏 𝑆𝑐

1 1 0 −12 0 1 −13 −1 1 04 −1 0 15 0 −1 16 1 −1 07 0 0 0

b

c

I

IIIII

IV

V VI

I3(−1 1 0)

I2(0 1 −1)

I4(−1 0 1)

I1(1 0 −1)

I5(0 − 1 1)

I6(1 − 1 0)

Iref

𝜃in a

Figure 4: Current space vectors of the rectifier.

The principle of space vectormodulation (SVM) is shownin Figure 4. 𝐼ref is the reference current space vector. 𝜃in is theangle of 𝐼ref .

According to the principle of space vector PWM,

𝑡1 =𝑚rec𝑇𝑠 sin (𝜋/2 − 𝜃in)

sin (𝜋/3),

𝑡2 =𝑚rec𝑇𝑠 sin (𝜃in − 𝜋/6)

sin (𝜋/3),

𝑡0 = 𝑇𝑠 − 𝑡1 − 𝑡2,

(4)

𝑑1 =𝑡1

𝑇𝑠

,

𝑑2 =𝑡2

𝑇s,

𝑑0 =𝑡0

𝑇𝑠

.

(5)

In (4), 𝑚rec is modulation index for the rectifier, whichcan be defined as

𝑚rec =𝐼ref𝐼dc

. (6)

In order to ensure the sinusoidal input current, themodulation index𝑚rec cannot be larger than 1,

𝑚rec ⩽ 1. (7)

In order tomaintain the input power factor as unity, phaseangle of 𝐼ref , 𝜃in should follow the phase angle of input spacevector voltage 𝑈in, so the voltage of dc-link is as follows:

𝑈dc = 𝑚rec ⋅ 𝑈in, (8)

𝑈in = 𝑢𝑎 + 𝑢𝑏 ⋅ e𝑗2𝜋/3

+ 𝑢𝑐 ⋅ e−𝑗2𝜋/3

. (9)

In (9), 𝑢𝑎, 𝑢𝑏, and 𝑢𝑐 are the three phase voltages of inputsides. In order to obtain the maximum voltage ratio of therectifier,𝑚rec should be 1.

The inverter is controlled as voltage source converter, andthe rectifier can be seen as a voltage source in dc-link. Theconventional SVPWM algorithm can be used in the inverter,shown in Figure 5:

𝑇1 =𝑚inv𝑇𝑠 sin (𝜋/3 − 𝜃)

sin (𝜋/3),

𝑇2 =𝑚inv𝑇𝑠 sin (𝜃)sin (𝜋/3)

,


1 1 10 0 0

I

II

III

IV

V

VI

Vref

V1 · T1

V2 · T2

𝜃

V5(1 0 0) V6(1 0 1)

V4(1 1 0)

V3(0 1 0) V2(0 1 1)

V1(0 0 1)

Figure 5: SVPWM for inverter when 0 < 𝜃 ≤ 𝜋/3.

𝑇0 = 𝑇𝑠 − 𝑇1 − 𝑇2,

𝐷1 =𝑇1

𝑇𝑠

,

𝐷2 =𝑇2

𝑇𝑠

,

𝐷0 =𝑇0

𝑇𝑠

,

𝑚inv =𝑈ref𝑈dc

.

(10)

In (10), 𝑇𝑠 is the period of a switching cycle. 𝑚inv is themodulation index of inverter. 𝐷0, 𝐷1, and 𝐷2 are the dutycycles of the zero vectors, vectors𝑉1 and𝑉2, respectively.𝑈refis the reference space voltage vector and 𝑈dc is the voltage ofdc-link.

From (8) and (9), when the input voltages are symmetri-cal, the voltage of dc-link is constant.Themodulation index ofinverter is determined by the reference output space voltagevector. The calculation of duty cycles 𝐷0, 𝐷1, and 𝐷2 will besimple.

2.2. Commutation and PWM Sequence. Generally, a bidi-rectional switch in matrix converters is constructed by twoIGBTs and two diodes or two RB-IGBTs. Commutationsbetween two bidirectional switches need four steps withvoltage/current signal. Figure 6 is the process of four-stepcommutation with voltage signal. 𝑡𝑐0, 𝑡𝑐1, 𝑡𝑐2, and 𝑡𝑐3 are thetimes for four-step commutation.

In IMC, the inverter is a conventional voltage sourceconverter and its commutation is traditional. When theinverter is on zero-vector state, the current of dc-link iszero. The commutation of the bidirectional switches in therectifier can be achieved during this period, and zero-currentswitching commutation can be realized. The PWM sequenceof IMC is shown in Figure 7 and ZCS commutation is shown

in Figure 8. 𝑡𝑐0 and 𝑡𝑐1 are the switching times for two-stepcommutation.

Compared with the conventional PWM algorithm [19–22], the proposed PWM algorithm increases one switchingaction in rectifier, which is a ZCS process. ZCS commutationis much simpler than four-step commutation and it needs novoltage or current signals. So voltage or current sensor in dc-link can be omitted.

2.3. Realization of SVMAlgorithm and CommutationMethod.In order to realize the SVM algorithm and commutationstrategy, a control platform based on DSP and CPLD isimplemented, shown in Figure 9. DSP TMS320F2812 of TIis to realize SVM algorithm and CPLD EPM9320LC84-15 ofAltera is to realize the commutation strategy for bidirectionalswitches in rectifier.

The input sectors Sci1∼Sci6 and output sectors Svo1∼Svi6are determined with the angle of input voltage and outputvoltage with DSP. And 8 PWM signals, which are shown inFigure 10, are generated by SVM and SVPWM algorithmswith DSP.The 8 PWM signals are not the drive signals for theIGBTs. A decoder for drive signals is needed. CPLD is usedto decode drive signals from PWM sequences and realizetwo-step ZCS commutation. With the PWM signals PWM1–8, input sectors, and output sectors, the drive signals for thebidirectional switches can be shown as expression (11), where𝑆𝑖+ is the upper bridge and 𝑆𝑖− is the lower bridge, 𝑖 = 𝑎, 𝑏, 𝑐.

According to the SVM algorithm for rectifier, the com-mutation of bidirectional switches occurs between the upperbridges (𝑆𝑎+, 𝑆𝑏+, 𝑆𝑐+) and lower bridges (𝑆𝑎−, 𝑆𝑏−, 𝑆𝑐−). FromFigure 4, the input current vector 𝐼1(1, 0, −1) will changeto 𝐼2(0, 1, −1), and the commutation is 𝑆𝑎+ to 𝑆𝑏+. Thecommutation process can be described by the state of RB-IGBTs in the rectifier [𝑆𝑎+ 𝑆𝑎− 𝑆𝑏+ 𝑆𝑏− 𝑆𝑐+ 𝑆𝑐−]. The pro-cess of commutation is [1 0 0 0 0 1]-[0 0 0 0 0 1]-[0 0 1 0 0 1]. Because the commutation is zero-currentswitching, the commutation of rectifier is the same asinverter. Only the dead time is needed:

𝑆𝑎+ = Sci1 + Sci6 ⋅ (1 ⊕ PWM2) + Sci2 ⋅ PWM1

+ Sci4 ⋅ (PWM1 ⊕ PWM2) ,

𝑆𝑎− = Sci4 + Sci3 ⋅ (1 ⊕ PWM2) + Sci5 ⋅ PWM1 + Sci1

⋅ (PWM1 ⊕ PWM2) ,

𝑆𝑏+ = Sci3 + Sci2 ⋅ (1 ⊕ PWM2) + Sci4 ⋅ PWM1

+ Sci6 ⋅ (PWM1 ⊕ PWM2) ,

𝑆𝑏− = Sci6 + Sci5 ⋅ (1 ⊕ PWM2) + Sci1 ⋅ PWM1 + Sci3

⋅ (PWM1 ⊕ PWM2) ,

𝑆𝑐+ = Sci5 + Sci4 ⋅ (1 ⊕ PWM2) + Sci6 ⋅ PWM1

+ Sci2 ⋅ (PWM1 ⊕ PWM2) ,

𝑆𝑐− = Sci2 + Sci1 ⋅ (1 ⊕ PWM2) + Sci3 ⋅ PWM1 + Sci5

⋅ (PWM1 ⊕ PWM2) .

(11)


Ua

Ub

Sap

Sap

tc0 tc1 tc2 tc3 tc0 tc1 tc2 tc3

Ua > Ub Ua < Ub

p

Sbp

Sbp

Spa Spa

Spb Spb

Sap

Sbp

Spa

Spb

Figure 6: Four-step commutation for bidirectional switches of RB-IGBT with voltage signal.

Inverter

Rectifier

Vector

Vector

0

0

1

d1 + d2

d1

d1

(D0/2 + D1 + D2)d1

(D0/2 + D1)d1

D0 · d2/2

V0 V0V0V1 V1V2 V2

d2(D0/2 + D1 + D2)d2(D0/2 + D1)d2

D0 · d1/2

Ts

I0I1 I2

Figure 7: PWM sequence for IMC.

Ua

Ub

SaSa

Sb

Sb

tc0 tc1

p

Sap

Sbp

Spa

Spb

Sap

Sbp

Spa

Spb

Figure 8: Two-step commutation for bidirectional switches of ZCS.

3. Power Factor Control of IMC

According to the SVM algorithm, power factor of IMC canbe controlled by changing the angle of the reference inputcurrent vector, shown in Figure 11. The phase difference ofcurrent vector and voltage vector is 𝜑 and power factor iscos𝜑.

It is assumed that, on the input side,

𝑢𝑎 = 𝑈𝑚 cos (𝜔𝑖𝑡) ,

𝑢𝑏 = 𝑈𝑚 cos(𝜔𝑖𝑡 −2𝜋

3) ,

𝑢𝑐 = 𝑈𝑚 cos(𝜔𝑖𝑡 +2𝜋

3) .

(12)

Table 2: Sectors of input current space vector.

Input sector Phase angle 𝜔𝑖𝑡1 [−𝜋/6, 𝜋/6)

2 [𝜋/6, 𝜋/2)

3 [𝜋/2, 5𝜋/6)

4 [5𝜋/6, 7𝜋/6)

5 [7𝜋/6, 3𝜋/2)

6 [3𝜋/2, 11𝜋/6)

And the reference input currents are

𝑖𝑎 = 𝐼𝑚 cos (𝜔𝑖𝑡 − 𝜑) ,

𝑖𝑏 = 𝐼𝑚 cos(𝜔𝑖𝑡 −2𝜋

3− 𝜑) ,

𝑖𝑐 = 𝐼𝑚 cos(𝜔𝑖𝑡 +2𝜋

3− 𝜑) .

(13)

The active power on input side is

𝑃 = 𝑢𝑎𝑖𝑎 + 𝑢𝑏𝑖𝑏 + 𝑢𝑐𝑖𝑐 =3

2𝑈𝑚𝐼𝑚 cos𝜑. (14)

From (14), 𝜑 is power angle. When 𝜑 > 0, IMC absorbsreactive power. When 𝜑 < 0, IMC generates reactive power.

From Figure 1, the inverter of IMC is voltage sourceconverter. The voltage of dc-link 𝑢pn should be positive.Otherwise, the reverse recovery diode for IGBTwill be short-circuited and the semiconductor may be damaged.

The sectors of input current space vector can be dividedby the angle of input voltage space vector, which is shown inTable 2.

According to Table 2, the corresponding relationship ofinput sector and input voltage interval is shown in Figure 12.Input sector I–VI is corresponding with voltage interval 1–6.In order to maintain the DC-link voltage being positive, therelationship of line voltage and phase angle in each sector isshown in Table 3.

In order to maintain the dc-link voltage being positive,the regulation range of 𝜑 is [−𝜋/6, 𝜋/6]. In the applicationsof power factor control, the parameter of input 𝐿𝐶 filters haseffect of power factor control. The simplified circuit of input𝐿𝐶 filters is shown in Figure 13.

In Figure 13, 𝑈𝑠 is input source voltage vector. 𝐼𝑠 isinput source current vector. 𝑈in and 𝐼in are input voltage


DSP TMS320F2812

CPLD EPM9320LC84-15

Input sector signal

Output sector signal

8 PWM signals

Sampling and regulating

Input voltages

Output currents

Zero crossing

12 drive signals for rectifier

Protection of IPM

Drive and protection circuit of RB-IGBT IPM

Over current protection

6 drive signals for inverter

ub

ua

uc

iAiBiC

Figure 9: Control platform based on DSP and CPLD.

Inverter

Rectifier

Ts

t1 t3t2 t4 t5 t6 t7 t8 t

PWM1

PWM2

PWM3

PWM4

PWM5

PWM6

PWM7

PWM8

Figure 10: PWM segments generated by DSP.

and current vector. Because 𝑈in will be influenced by SVMalgorithm,𝑈𝑠 is used as the reference input voltage vector. 𝐼inis the reference input current vector. The parameters of input𝐿𝐶 filters are 𝐿𝑎 = 𝐿𝑏 = 𝐿𝑐 = 𝐿 = 0.7mH, 𝐶𝑎 = 𝐶𝑏 =

𝐶𝑐 = 𝐶 = 20 𝜇F. Assume that input source voltage vector is𝑈𝑠 = 𝑈𝑚∠𝛼 and input current vector is 𝐼in = 𝐼𝑚∠(𝛼 − 𝜑).𝐼𝑚 is decided by the load current and can be calculated withthe modulation index of IMC and the amplitude of outputcurrents.

a

b

c

𝜑

Iref

U

Figure 11: The principle of power factor control.

From Figure 13, the differential equations for 𝐿𝐶 filterscan be built as follows:

𝑈𝑠 − 𝑈in = 𝐿𝑑𝐼𝑠

𝑑𝑡,

𝐼𝑠 − 𝐼in = 𝐶𝑑𝑈in𝑑𝑡

.

(15)

Then, the input source current 𝐼𝑠 is as follows:

𝐿𝐶𝑑2𝐼𝑠

𝑑𝑡2+ 𝐼𝑠 − (𝐼in + 𝐶

𝑑𝑈𝑠

𝑑𝑡) = 0. (16)


1 2 3 4 5 6

ubua uc

t

U

(a) Input voltage intervals

I

IIIII

IV

V VI

I3(−1 1 0)

I2(0 1 −1)

I4(−1 0 1)

I5(0 − 1 1)

I6(1 − 1 0)

I1(1 0 −1)

b

a

c

(b) Sector of input current space vector

Figure 12: Input voltage interval and sector of input current space vector.

Table 3: Relationship of line voltage and phase angle.

Sector Line-line voltage Phase angle 𝜔𝑖𝑡1 𝑢𝑎𝑏 ≥ 0 𝑢𝑎𝑐 ≥ 0 [−𝜋/3, 𝜋/3)

2 𝑢𝑎𝑐 ≥ 0 𝑢𝑏𝑐 ≥ 0 [0, 2𝜋/3)

3 𝑢𝑏𝑐 ≥ 0 𝑢𝑏𝑎 ≥ 0 [𝜋/3, 𝜋)

4 𝑢𝑏𝑎 ≥ 0 𝑢𝑐𝑎 ≥ 0 [2𝜋/3, 4𝜋/3)

5 𝑢𝑐𝑎 ≥ 0 𝑢𝑐𝑏 ≥ 0 [𝜋, 5𝜋/3)

6 𝑢𝑐𝑏 ≥ 0 𝑢𝑎𝑏 ≥ 0 [4𝜋/3, 2𝜋)

Is Iin

Uin

La

Lb

Lc

CcCbCa

Us

Figure 13: Simplified circuit of input 𝐿𝐶 filters.

Considering the fundamental part of input current andignoring harmonics current and dynamic process, inputsource current is expressed as 𝐼𝑠 = 𝐼𝑥∠𝛽. From (16),

𝐼𝑥 (1 − 𝐿𝐶𝜔2𝑖 ) ∠𝛽 = 𝐼𝑚∠ (𝛼 − 𝜑)

− 𝐶𝜔𝑖𝑈𝑚∠(𝛼 −1

2𝜋) .

(17)

Figure 14: Prototype of RB-IGBT based indirect matrix converter.

The amplitude and angle of input source current can begot as follows:

𝐼𝑥 =

√(𝐼𝑚)2+ (𝐶𝜔𝑖𝑈𝑚)

2− 2𝐶𝜔𝑖𝑈𝑚𝐼𝑚 sin𝜑

1 − 𝐿𝐶𝜔2𝑖

,

𝛽 = 𝛼 + arctan(𝐶𝜔𝑖𝑈𝑚 − 𝐼𝑚 sin𝜑

𝐼𝑚 cos𝜑) .

(18)

From (18), power angle is related to the capacitor of𝐿𝐶 filters, the amplitude of load current, and the angle ofreference input current vector.

4. Experimental Results

The prototype of RB-IGBT based indirect matrix converterhas been developed, shown in Figure 14. It mainly includespower circuit, RB-IGBT gate drive circuit, signal processingcircuit, CPLD and DSP based control board, and heatsink. The rectifier is composed of the RB-IGBT module18MBI100W-060A from Fuji Electric [31].


T

(a) Input phase voltage (25V/div) and current (5 A/div)

T

(b) Output line-to-line (25V/div) and current (5 A/div)

Figure 15: Experimental waveforms of proposed PWM algorithm.

T

Figure 16: The voltage (25V/div) across RB-IGBT and the dc-linkcurrent (5 A/div) during zero-current switching.

In order to verify the proposed PWM algorithm andsequence, experimental tests on IMC prototype have beencarried out. The parameters of the input filters are 𝐿 =

0.7mH,𝐶 = 20 𝜇F, and𝑅 = 200Ω.The sampling frequency is10 kHz. Input voltage is 50Hz and output frequency is 25Hz.The load is an induction motor.

Figure 15 gives the experimental waveforms of SVMalgorithm. The THD of output current is 1.06%. The THDof input current is 6.39%. Figure 16 shows the voltage of thebidirectional switch 𝑆ap-𝑈sap and dc-link current 𝑖dc when thecommutation of bidirectional switches occurs. It can be seenthat dc-link current is around zero at the commutation point,which means that zero-current switching is realized.

The waveforms of input voltage and current when thepower factor angle is setting as −2𝜋/15, zero, and 2𝜋/15 areshown in Figures 17–19, respectively.

The power factor angle of experiment can be shown inTable 4. The theoretical value of power factor angle can becalculated by expression (18).

T

Figure 17: The experiment waveforms of input (25V/div) andcurrent (5 A/div) when power factor angle is −2𝜋/15.

Table 4: Comparison of theoretical value and experimental resultof power factor angle.

Setting powerfactor angle Calculated by (18) Experimental result

𝜑 = −24∘

−26.3∘

−28.8∘

𝜑 = 0 −7.7∘

−14.4∘

𝜑 = 24∘

14∘

10.8∘

5. Conclusions

In this paper, a SVM algorithm for indirect matrix converterwith zero-current switching commutation for bidirectionalswitches is realized based on a control platform of DSP andCPLD. SVM for the rectifier and SVPWM for the inverterstage are described. PWM sequence of the SVM algorithmcan achieve two-step ZCS commutation for the rectifierbidirectional switches. The realization of PWM sequence byDSP and decoding process for drive signals of RB-IGBTs byCPLD are explained in detail.


T

Figure 18: The experiment waveforms of input (25V/div) andcurrent (5 A/div) when power factor angle is zero.

T

Figure 19: The experiment waveforms of input (25V/div) andcurrent (5 A/div) when power factor angle is 2𝜋/15.

Based on the modulation strategy, input power factorcorrection of IMC is discussed. Because the inverter ofIMC is VSI, the dc-link voltage should be positive and theregulation range of power angle is [−𝜋/6, 𝜋/6]. The influenceof the parameters in 𝐿𝐶 filters is analyzed. A prototype ofRB-IGBT based indirect matrix converter is implemented.The experimental results show the performance of SVMalgorithm and validate the analysis of power factor controlof IMC.

Conflict of Interests

The author declares that there is no conflict of interestsregarding the publication of this paper.

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