uhf-rfid wireless control system modeling and...
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215 Khomdram Jolson Singh, Dhanu Chettri, Th. Jayenta Singh
International Journal of Electronics, Electrical and Computational System
IJEECS
ISSN 2348-117X
Volume 6, Issue 3
March 2017
ABSTRACT
This Paper presents the analysis and simulation of UHF RFID
system in Matlab/Simulink environment. The simulation is
divided into the transmitter, channel and receiver part. Some
Negative effects are concerned in the system model, such as
phase noise, reflection of the environment, AWGN noise, I/Q
mismatch, etc. The architecture of the model is described in
details, and is flexible to achieve different modulation and
encoding types. Finally, the results of the simulation are
presented and analysed. These result will be very helpful for the
further development work of RFID system.
Index Terms— RFID, ASK, Manchester coding, Gaussian
noise, modelling and simulation.
I. INTRODUCTION
ost of the Radio Frequency Identification (RFID)
systems used radio frequency to automatically
identify products. RFID system consists of two
modules namely Reader and Tag. The different
frequencies used for transmission are classified into the
four basic ranges, LF (low frequency, 100-500 KHz), HF
(high frequency 1-400 MHz), UHF (Ultra high frequency,
850-950 MHz) and microwave (1-5.8 GHz). For LF and
HF RFID, the scan distance is upto 10 cm and 1 m
respectively. For microwave RFID, because of the
sensitivity to the environment, the maximum reader range
is about 10 m. For UHF RFID, the read range can
generally reach to 7 m. Further, the RFID system can be
classified into active RFID (Tag with battery) and passive
RFID (Tag without battery). In this paper, we discuss only
the passive UHF RFID system. For a passive RFID, first
the Reader should send out electromagnetic waves to
wake-up the Tag, and then transmit the modulated wave to
command Tag. A passive tag absorbs power from the field
created by the reader and uses it to power the microchip's
circuits. Then Reader transmits continuous wave (CW),
while Tag backscatters the information. There are many
protocols about UHF RFID, in this paper, the simulation is
mainly based on EPC Class 1 and EPC Class 1 Generation
2 UHF RFID (abbreviate as Gen 2) protocols.
Figure 1 A complete generalized RFID system
II. MODELLING AND SIMULATION
The following figure shows a block diagram of our
model
Figure 2 Schematic of RFID simulink Model
The Simulink® platform developed by MathWorks was
used to build our models. The input data consists of binary
1s and 0s, which are modulated using amplitude shift
keying (ASK). The signal power level can be adjusted, and
the signal attenuation due to orientation or distance can be
varied. Environmental noise is modeled in terms of
random Gaussian noise. The signal that traverses the
transmission channel is subsequently decoded to form the
received signal.
For the first set of simulation runs, the data is coded using
NRZ coding and later by Manchester coding. The data
sent and received are compared and the number of tags
read correctly determined, thereby obtaining the read
reliability under the varying factors.
In this paper, a system model is developed with some
simulation results. At first, the simulation model is
introduced briefly. Models of DSP, transmitter and
wireless channel, front-end of tag and receiver model are
introduced. Finally,
UHF-RFID Wireless Control System Modeling and
Simulation
M
Khomdram Jolson Singh, and Dhanu Chettri and Th. Jayenta Singh Department of Electronics and Communication Engineering, Manipur Institute of
Technology, Takyelpat, Imphal, Manipur, INDIA
216 Khomdram Jolson Singh, Dhanu Chettri, Th. Jayenta Singh
International Journal of Electronics, Electrical and Computational System
IJEECS
ISSN 2348-117X
Volume 6, Issue 3
March 2017
Figure 3 Complete RFID system design in SIMULINK
some simulation results are presented. There are some
critical problems to be discussed. The raised cosine filter
affects the spectrum of the output, and the parameters
should be handled carefully. The SSB transmission is not
very ideal from the simulation results since a finite length
of data is processed. In receiver of reader, the suppression
of DC offset and transient response may drive the follow-
up circuits into saturation. The bandwidth of channel
select filters is also important because it is related to noise
floor. Baseband circuits, variable gain stage and detector
of receiver are also challenges. The reflection of the
objects in environment will mainly affect the operation of
tag, and special attention should be paid to diminish the
effect of Fresnel zones. All the problems mentioned above
should be solved in further study and cost much of efforts
to get a best performance. The system simulation is
focused on reader side with a simple wireless channel and
a simple reflection model of tag for evaluating the
performance of reader. More complicated models should
be constructed in frequency domain simulation to
determine and optimize the parameters of building blocks
of reader and tag.
A. Transmitter
When you Forward Link Encoding. In both the Class
1 and the Gen 2 protocols, binary data from Reader to Tag
is encoded as Manchester Encoding of the low amplitude
pulse.
Figure 4 Subsytem of Reader showing Demodulator for
RX and different Carrier signals used for TX.
B. Encoding
Data embedded within RFID tags consists of n bits of
data, with each bit either a binary 1 or 0. Some of the
frequently used encoding for the transmission of binary
data includes Unipolar, NRZ, Unipolar RZ, Bipolar and
Manchester coding. Presently, the data stored in RFID tags
are typically coded using Unipolar (also commonly known
as on-off keying), polar, Unipolar return-to-zero, or
Manchester coding (as shown in the figure below).
Some methods of encoding are better than others in
terms of error detection. The superiority of the Manchester
coding as compared to the NRZ coding is evident in the
case of a collision. Consider a tag using the NRZ
encoding. Transponder 1 transmits the bit stream
10110010, while transponder 2 transmits 10011100. The
signal received by the signal is 10111111, which does not
correspond to either of the bit streams transmitted by
transponder 1 or 2. The reader is not aware that an error
has occurred - undetectable collision has occurred.
Figure 5 Different types of coding
If Manchester encoding was used instead, collisions
might result in a steady state period. As transitions have to
217 Khomdram Jolson Singh, Dhanu Chettri, Th. Jayenta Singh
International Journal of Electronics, Electrical and Computational System
IJEECS
ISSN 2348-117X
Volume 6, Issue 3
March 2017
occur in Manchester encoded signals, the steady state
period that results is an indication that an error has
occurred.
Figure 6 Detection of collision
Figure 7 Subsystem model for Manchester Encoding
Figure 8 Waveforms of Binary ID input signal and its
Manchester Encoded signal.
Figure 9 Power Spectral Density (PSD) of the
Manchester Encoded Signal
C. Modulation
In Class 1 protocol, the reader shall communicate with
the tag by Amplitude Shift Keying (ASK) modulation, and
the modulation depth is from 30% to 100%. In Gen 2
protocol, the reader shall use double-sideband amplitude
shift keying (DSB-ASK), single-sideband amplitude shift
keying (SSB-ASK) or phase-reversal amplitude shift
keying (PR-ASK), and the modulation depth is from 80%
to 100%. By the architecture of the simulation model, it
can implement all these modulation types.
Figure 10 Complete waveform obtained from the ASK
modulator used in our RFID system model
D. Reciever
Return Link Encoding: In Class 1 protocol, Tags reply
to Reader commands with backscatter modulation with the
encode form shown in below, where two transitions are
observed for a binary zero and four transitions are
observed for a binary one during one Bit Cell. In Gen 2
protocol, Tags shall encode the backscattered data as
either FM0 baseband or Miller modulation of a subcarrier
at the data rate. The Reader selects the encoding type
Figure 11 Demodulator subsystem Model with Digital
Filter for RX in reader
Figure 12 Direct Form Digital FIR filter design used
for final Tag ID recovery.
218 Khomdram Jolson Singh, Dhanu Chettri, Th. Jayenta Singh
International Journal of Electronics, Electrical and Computational System
IJEECS
ISSN 2348-117X
Volume 6, Issue 3
March 2017
Figure 13 Different waveforms showing the recovery of
Tag ID from ASK Modulated Signals.
III. CALCULATIONS
A. Free Pass Loss
Free Space Path Loss. In telecommunication, free-space
path loss (FSPL) is the loss in signal strength of
an electromagnetic wave that would result from a line-of-
sight path through free space (usually air), with no
obstacles nearby to cause reflection or diffraction. It does
not include factors such as the gain of the antennas used at
the transmitter and receiver, nor any loss associated with
hardware imperfections.
The formula of the free space pass loss is
)(lg20)(lg2045.32)( KmdMHzfdbLs
Where „f‟ is the carrier frequency „d‟ is the distance
between Reader and Tag.
Figure 14 Inside the communication channel system
model with different noises such as AWGN and Free
Space Path Loss
A convenient way to express FSPL is in terms of dB
))4
((log10)( 2
10 dfc
dBFSPL
)4
(log20 10 dfc
)4
(log20)(log20)(log20 101010c
fd
55.147)(log20)(log20 1010 fd
Where the units are as before.
For typical radio applications, it is common to find f
measured in units of GHz and d in km, in which case the
FSPL equation becomes
45.92)(log20)(log20)( 1010 fddBFSPL
For fd, are in meters and megahertz, respectively, the
constant becomes 55.27
B. Additive white Gaussian noise (AWGN)
It is a channel model in which the only impartment to
communication is a linear addition of wideband or white
noise with a constant spectral density (expressed as watts
per hertz of bandwidth) and Gaussian distribution of
amplitude. The model doesn‟t account for fading,
frequency selectivity, interference, linearity or dispersion.
However, it produces simple and tractable mathematical
models which are useful for gaining insight into the
underlying behavior of a system before these other
phenomena are considered.
Signal to noise ratio (SNR), where the block calculates the
variance from these quantities that you specify in the
dialog box:
SNR, the ratio of signal power to noise power
Input signal power, the actual power of the samples at the
input of the block
Changing the symbol period in the AWGN Channel block
affects the variance of the noise added per sample, which
also causes a change in the final error rate.
For complex input signals, the AWGN Channel block
relates Eb/N0, Es/N0, and SNR according to the following
equations:
Es/N0 = (Tsym/Tsamp) · SNR
Es/N0 = Eb/N0 + 10log10(k) in dB
Where
Es = Signal energy (Joules)
Eb = Bit energy (Joules)
N0 = Noise power spectral density (Watts/Hz)
Tsym is the Symbol period parameter of the block in Es/No
mode
k is the number of information bits per input symbol
Tsamp is the inherited sample time of the block, in seconds.
For real signal inputs, the AWGN Channel block relates
Es/N0 and SNR according to the following equation:
Es/N0 = 0.5 (Tsym/Tsamp) SNR
C. Backscatter
In the return link, Tag communicates with the Reader by
backscatter modulation. During backscatter Reader
transmits an un-modulated continuous wave (CW) signal,
219 Khomdram Jolson Singh, Dhanu Chettri, Th. Jayenta Singh
International Journal of Electronics, Electrical and Computational System
IJEECS
ISSN 2348-117X
Volume 6, Issue 3
March 2017
then Tag modulates its reflection of the CW signal. In
Class 1 protocol, Tag modulates the amplitude of the
carrier (ASK). In Gen 2 protocol, Tag modulates the
amplitude and/or phase of the carrier (ASK and/or
PSK).Modulation of the backscattered wave is achieved
by changing the tag IC‟s input impedance between two
different states ZR_jX and ZR _ jX.
For ASK, it is achieved by a change in the real part of the
impedance and of the reflection coefficient. And PSK is
achieved by changing the imaginary part of the input
impedance and of the reflection coefficient. In this paper,
it will only discuss the ASK case.
D. Tag Received Power
In forward link, the output power is
TXPAEIRP GPP
The Effective Isotropic Radiated Power (EIRP) of the
reader is PEIRP. The typical maximum output power is
500mW, 2W (ERP, CEPT) and 4W (EIRP, FCC).
Converted to dBm, the permitted maximum limits are
about 29dBm (500mW ERP, 825mW EIRP), 35dBm (2W
ERP, 3.3W EIRP) and 36dBm (4W EIRP). GTX is the
gain of the transmitter antenna. The typical value is
assumed to be 6dBi. Therefore, the maximum output
power from power amplifier should be 23dBm, 29dBm
and 30dBm, respectively.
The power transmitted from reader to tag can be expressed
as
22 )4
()4
(d
GPd
GGPP tagEIRPtagTXPArec
λ is the wavelength of the carrier. d is the distance from
reader to tag.
E. Tag Reflection Model
As we all know, tag received power includes two parts, the
reflected power and the available power can be used by
the chip. The distribution of these, two parts is very
critical for a maximum distance. In [7]
a detail calculation is performed.
The available power from antenna can be used by the
rectifier is
2,,21,,1, inRFinRFinRF PpPpP
)]||1()||1([8
2
22
2
11
2
0 ppR
v
ant
The reflect power is
radbs RiiP 2
21 ||8
1
0v is the peak source voltage that would be observed if the
antenna were not loaded by the IC. In time domain, the
probabilities that chip in state 1 and state 2 are p1 and p2.
ρ1, 2 are the reflection coefficients. Rant is the real part of
the antenna impedance. 21 & ii are the current flow
through the impedance. radR is radiation impedance of
antenna.
Figure 15 RFID Tag Subsystem
F. Demodulation
As analysis above, the Tag reflection power is much
weaker than the Reader transmit power, and Reader
transmits CW signal
IV. RESULT AND DISCUSSION
As shown above, the IDs are well recovered from the
noisy Manchester code stream. Comparing with the source
IDs, the recovered just have a time delay. In the
simulation, we adjusted the noise power in the model to
obtain the Bit Error Rate (BER) by the Error Rate
Calculation block. Their results (not shown in this thesis)
indicate that when the SNR >=1:0 dB, the BER is still
zero, which implies a good performance of the simulation
proposed in this thesis.
Figure 16 Comparison of Transmitted ID data with
Recovered ID Data.
Figure 7 Close-Up Waveform of Recovered ID Data
showing a small phase delay from transmitted Id data.
V. CONCLUSION
An UHF passive RFID system have been designed and
simulated using Matlab/Simulink environment. Some
Negative effects such as phase noise, reflection of the
environment, AWGN noise, I/Q mismatch etc. are also
220 Khomdram Jolson Singh, Dhanu Chettri, Th. Jayenta Singh
International Journal of Electronics, Electrical and Computational System
IJEECS
ISSN 2348-117X
Volume 6, Issue 3
March 2017
taken into account in the system model. The architecture
of the model is described in details which is flexible to
achieve different modulation and encoding types. Finally,
the results of the simulation are presented and analysed.
These result will be very helpful for the further
development work of RFID system.
REFERENCES
[1] MIT Auto-ID Center Publications:
http://www.autoidcenter.org
[2] Daniel W. Engels, “The Reader Collision Problem”, MIT-
AUTOID-WH 007
[3] EPC Radio-Frequency Identity Protocols Generation 2
Identity Tag (Class 1): Protocol for Communications at
860MHz-960MHz. EPC Global Hardware Action Group (HAG),
EPC Identity Tag (Class 1) Generation 2, Last-Call Working
Draft Version 1.0.2, 2003-11-24
[4] John G. Proakis, “Digital Communications (Fourth
Edition)”, McGraw-Hill Companies, Inc, 2001
[5] Behzad Razavi, “RF Microelectronics”, Prentice Hall, Inc.
1998
[6] David Johns, Ken Martin, “Analog Intergrated Circuit
Design”, John Wiley & Sons, Inc, 1997
[7] Udo Karthaus,Martin Fischer,“Fully Integrated Passive
UHF RFID Transponder IC With16.7-uW Minimum RF Input
Power”, IEEE Journal of Solid-State Circuits, Vol.38, No. 10,
October 2003.
[8] The Palomar system Deliverable D7, Version V2.1,2002
[9] European Standard (Telecommunications series),
“Electromagnetic compatibility and Radio spectrum Matters
(ERM); Radio Frequency Identification Equipment operating in
the band 865MHz to 868MHz with power levels up to 2W; Part
1: Technical requirements and methods of measurement”, Draft
ETSI EN 302 208-1 V1.1.1, 2003-