201606_ferrites,_cmc,_and_power_transformer_(2)e
TRANSCRIPT
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Soft Ferrite SpecificationCMC、 Power Choke
and Transformer(A)Soft Ferrite(B)CMC(C)Power
Choke/TransformerBy Ray LaiJune 2016
Table of ContentB.CMC
B1. CMC PrincipleB2. CMC DesignB3. CMC Failure Example
C.Power Choke and TransformerC1. Power ChokeC2. Coupled Inductor (Flyback Transformer)C3. SMPS Transformer
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B. Common mode choke CMC)3
Magnetic components play key role in power conversion system
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B. Common mode choke (CMC)
Magnetic components which ferrites can make
5 Input side CMC generally adopts closed-loop core (toroid) or ET core. On the high frequency output side, HI configuration is also popular (usually mirror lapping required, easy for auto winding)
Hi-Lo side isolation is required by the spacers of bobbin
B. Common mode choke (CMC)
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B. Common mode choke (CMC)
SMD Pulse Transformer SMD Common Mode Choke
Conventional Newer
磁環
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B1. CMC Principle CMC is used to filter out the “common mode” noise with the minimal effect on the main electrical quantity (no matter signal or power) (EN55022 requires EMI conduction reduction in 150kHz~500kHz)
Two independent choke(Two cores)
CMC(One core)
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B1. CMC Principle
Ampere’s right-hand rule
The main (load) current flows opposite direction in the two windings, so its flux canceled each (differential mode), only leakage can cause the core to saturate.
CM noise generates flux in the same direction, so it sees high impedance
: noise frequency ,L: CM inductance
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Measurement of common mode
Measurement of differential mode (leakage)
Why “Peak” frequency different?
Parasitic C of windings
B1. CMC Principle
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L 1 2 0
1 2
0
3
K
COUPLING=
K 2
1TX2 2 _ 1 4 _ 1 3 _ 3 E 2 7
L 1 = L 2
K
COUPLING=
K 1
1TX2 2 _ 1 4 _ 1 3 _ 3 E 2 7
L 1 = L 1R 17 5 0
2
V 1
TD = 0
TF = 1 uP W = 4 9 uP E R = 1 0 0 u
V 1 = -1
TR = 1 u
V 2 = 1
L 2 2 01 2
R 2
0 . 1
R 3
0 . 1
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Q: WHY?
A: Inductor is a LP filter itself
B1. CMC Principle
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1
L 1 2 0
1 2
0
K
COUPLING=
K 1
1TX2 2 _ 1 4 _ 1 3 _ 3 E 2 7
L 1 = L 1
L 2 = L 2R 17 5 0
2
V 1
TD = 0
TF = 1 uP W = 4 9 uP E R = 1 0 0 u
V 1 = -1
TR = 1 u
V 2 = 1
L 2 2 01 2
R 2
0 . 1
R 3
0 . 1
B1. CMC Principle
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B2. CMC Design The impedance of CMC (resistance and reluctance) are from the complex permeability of the material (u‘ and u“), and the frequency of u’ is the key to CMC design
13 Ignoring the wiring resistance, (leakage) inductance, and parasitic capacitance, the impedance of CMC is
Using Q as the quality index of CMC or power choke must consider its load situation ( and frequency, voltage)
Q in power and signal level are not equivalent to each other!
Core loss factor
B2. CMC Design
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Critical in common mode choke design selection
𝜇𝑖× 𝑓𝑟𝑒𝑞𝑢𝑛𝑒𝑐𝑦 ≈𝑐𝑜𝑛𝑠𝑡𝑎𝑛𝑡
B2. CMC Design
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where:fg – gyromagnetic critical frequencyγ ~0.22 ΜΗz m/A is the gyromagnetic ratio for an electron
i.e. the ratio of magnetic moment and torqueBs – saturation flux densityμi,0– initial permeability * J. L. Snoek, Physica 14, 207, 1948
sig Bf 34)1( 0, Snoek Limit
A2. Specifications – Power/High Perm Materials
For higher perm material to have wider frequency response is against the law of physics.
16 Characteristics of Mn-Zn and Ni-Zn Ferrite in the sense of ui vs. frequency All governed by Snoek limit.
A2. Specifications – Power/High Perm Materials
Limit is here roughly by the advances of ferrite research
17 CMC is in transformer configuration (coupled inductor) yet is not used in transformer way
Usually by adding a pair of small capacitor (Y capacitors) on the AC input side to form an L-C low pass filter can suppress the noise better
the L2-C configuration will have -3dB corner frequency
low pass corner frequency.
The parasitic capacitor affects the performance (by changing |Zcmc| in a more complex way
B2. CMC Design
18 Case 1: A10EP7L failed in 150k~200kHz EMI conduction
Z_peak @ 300kHz?!
Turns’ number: 80
B2. CMC Design
19 Case 1: A10EP7L failed in 150k~200kHz EMI conduction
By material u’ and u”, the frequency of Z_peak > 1MHz
B2. CMC Design
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The parasitic capacitance cannot be ignored in this case
𝑍 𝑐𝑜𝑟𝑒=(𝑁2 𝜔𝜇0
𝐴𝑒
𝑙𝑒)¿
𝑍 𝑐𝑎𝑝=1/ 𝑗𝜔𝐶𝑝
|𝑍𝑐𝑜𝑟𝑒|=|( 1𝑍𝑐𝑜𝑟𝑒
+ 1𝑍𝑐𝑎𝑝 )
− 1|
Case 1: A10EP7L failed in 150k~200kHz EMI conduction
B2. CMC Design
21 Case 1: A10EP7L failed in 150k~200kHz EMI conduction
Just by 4pF, the amplitude and peak of the impedance of CMC totally changed
B2. CMC Design
22 Case 1: A10EP7L failed in 150k~200kHz EMI conduction
In the end, it is A05-90T that works!
B2. CMC Design
23 Case 1: A10EP7L failed in 150k~200kHz EMI conduction
In the end, it is A05 that works!
Measurement matched the calculation from the material table
B2. CMC Design
24 Case 2 : Geometric Fantasy of CMC
Due to the size and material limitation, someone was thinking if bigger Ae (or higher Ae/le) available by the following topology change.
To replace the simple toroid
B2. CMC Design
25
As long as the windings are still on two sides of the core, any of the above ways cannot increase Ae or yield more flux passing surface. Only increase the leakage of the CMC which is unwanted.
B2. CMC Design Case 2 : Geometric Fantasy of CMC
The same for this one
B2. CMC Design Case 2 : Geometric Fantasy of CMC
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If winding are on the center part, than the right (EE) and left cores are equivalent.
Q: Why did not see CMC doing this way?A: next page
B2. CMC Design Case 2 : Geometric Fantasy of CMC
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High-low side insulation is the basic safety regulation requirement.
B2. CMC Design Case 2 : Geometric Fantasy of CMC
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High Permeability Material List for CMC [ACME]
Symbol UnitMeasuring Conditions High Permeability Materials
Freq. Flux den. Temp. A05 A07 A071 A10 A102 A121 A151
Initial Permeability μi ≤ 10KHz 0.25mT 25°C 5000± 25%
7000± 25%
7000 ± 25%
10000± 30%
10000± 30%
12000± 30%
15000± 30%
Realative Loss factortan δ/μi 10-6
10KHz< 0.25mT 25°C < 4 < 8 < 8 < 10 < 10 < 10 < 10
100KHz < 15 < 30 < 30 < 60 < 60 < 60 <110Saturation Flux Density
Bms mT 10KHz H=1200A/m
25°C 440 400 440 410 380 380 400100°C 300 200 280 210 180 180 170
RemanenceBrms mT 10KHz H=1200A/
m25°C 80 150 80 140 95 130 220
100°C 90 110 60 110 75 110 100
Temperature Factor of Permeability αF 10-6/°C 10KHz < 0.25mT
0~20°C 0~2 -1 ~ 1 -1~1 0~1.5 -1 ~ 1 0~1.5 -1~120~70°C 0~2 -1 ~ 1 -1~1 -0.5 ~ 1 -1 ~ 1 -0.5~1 -1~1
Hysteresis Material Constant ηB 10-6/mT 10KHz 1.5-3.0mT 25°C < 0.8 < 1.2 < 1.2 < 0.5 < 1 < 0.5 < 0.5
Disaccommodation Factor DF 10-6 10KHz < 0.25mT 25°C < 3 < 2 < 2 < 2 < 2 < 2 < 2
Curie Temperature Tc °C 140 130 ≥ 145 130 120 110 110Resistivity ρ Ωm 0.2 0.35 0.35 0.15 0.15 0.12 0.1
Density d g/cm3 4.85 4.9 4.9 4.9 4.9 4.9 5
AutomotiveRecommended
B2. CMC Design
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u
ZThis point is by LC parallel resonance, where L is pure winding, C is layer parasitic. Baiscally it becomes space EM issue, nothing to do with ferrite.
Solution: (1) increase layer space (2) change wire diameter (3) change turns number or core size
B2. CMC Design
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Winding is a kind of art, the unique technic for winding house to survive
B2. CMC Design
Not really there
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Winding experiment from BW ( 百徽 ) engineer (2014-06-27 data)
B2. CMC Design
33
Useless and way of winding dependent.
B2. CMC Design
34
B3. CMC Failure Example Failed replacement attempt: - A12URT19C
Trying to use the custom made A12URT19C to replace A10T20x11x10C, but the customer found when the load current > 3A, CMC failed like not there.
1. To replace, check if Ae/le is better first, as least should be equivalent.
For T20x11x10C, Ae/le=0.951 only 21 turns needed for A10 to have 5mH low frequency inductance
Outer D Inner D Height d1 d2 h mm 20 11 10 NominalNominal C1 1.051E+00 mm^-1 uo 1.25664E-06C2 2.406E-02 mm^-3 ui 10000Le 45.911 mm AL 1.19567E-05Ae 43.683 mm^2 N 21Ve 2,005.527 mm^3 L 5.273E-03
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The Ae/le of URT19C is 0.263 , A12 takes 36 turns to have the 5mH
Geometrically, URT19C fails!
B3. CMC Failure Example
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2. Check if new material yields a better frequency response
B3. CMC Failure Example
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2. . Check if new material has better frequency response EN-55022 EMI Conduction frequency range is 150kHz~500kHz ,A12URT19C fails!
B3. CMC Failure Example
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3. For current > 3A, CMC lost its function, the conduction noise like the case of no CMC
Only leakage will cause CMC to saturate then fail
B3. CMC Failure Example
à R12k (27Ts) A07(A121 36Ts) A10 (31Ts)
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B3. CMC Failure Example
3. For current > 3A, CMC lost its function, the conduction noise like the case of no CMC
Only leakage will cause CMC to saturate then fail
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B3. CMC Failure Example
3. For current > 3A, CMC lost its function, the conduction noise like the case of no CMC
Only leakage will cause CMC to saturate then fail
4. ui and bandwidth of A12 is inferior than R12K (in this case), by the same core A12 of 36 turns equals to 27 turns of R12. Surely A12 has more leakage.
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B3. CMC Failure Example
4. By comparing the datasheet, A12 is as good as R12K (though not fully sintered), but sometimes it is just not the case in real product.
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B3. CMC Failure Example
43 Big part of MnZn CMC complaints, beside Z and bandwidth, are related to the coating damage caused by winding process (NiZn has no this issue)
Flux linkage from load current cancels each other, so the differential voltage across CMC =0
B3. CMC Failure Example
44
When short happens, due to high is high thus it will cause sparks or even crack the core when the coating insulation cannot sustain.
B3. CMC Failure Example
45
When windings are partially shorted, if the coating layer sustains, the imbalance on the MMF will heat up the core till it breaks down.
B3. CMC Failure Example
46
B3. CMC Failure Example
When windings are partially shorted and the coating layer broken, the instantaneous high current may cause the core to explode.
47 EN55022 specifies the EMI/EMC regulation, in HF band, NiZn is used and it’s the winding skill that matters most, beside the ferrite property.
B. Common mode choke (CMC)
48
C. Power Choke and Transformer Frequent asked questions:1. When measuring core loss of a gapped part, it is much higher
than calculating it using the core curves in the catalog. WHY?(explained)
2. How to derive the core height from a fixed core footprint for a given power level in power transformer? Or for a fixed core geometry, what is the most fit height for maximal power density?
This is a difficult to answer question and might be no answer. The only certain thing is that for a fixed core geometry, there is a maximal power density it can go for two-winding model (and it is SMPS topology dependent), there is no universal formula for any winding number and any switching topologies.
Switching transformer design is still a case-by-case issue to make the engineer’s career interesting.
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2. How to derive the core height from a fixed core footprint for a given power level in power transformer? Or for a fixed core footprint, what is the most fit height for maximal power density?
Even better winding arrangement can increase the power handling capability of a transformer in the sense of temperature rise.
C. Power Choke and Transformer
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C. Power Choke and Transformer
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Ci
CoN2
N1
D1
Ci
D2
LR
S1
2
1
3
S2
2
1
3
N2
Vo
>iL
-
+
-
-
++
Vi Vin
12
RloadCD
LSW2
1
3
+ +
--
Vo
+ -
For the below half-bridge converter, its equivalent is a buck converter, with Vin=10V, Vout=5V, Pout=100W, and switching frequency= 100kHz. Determine the inductance and design the inductor.
Half-Bridge Converter is a Buck Topology
Note: In practical design, there are many factors to consider. There is some degree of freedom in choosing the core type, but not with no limitation at all.
C1. DC-DC Power Choke
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C1. DC-DC power choke
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Vin
12
RloadCD
LSW2
1
3
+ +
--
Vo
+ -
Assuming CCM mode,
Then the V-I relationships are
where and
is called voltage regulation and is determined by L and C.
=
C1. DC-DC power choke
54
time
S1 on S1 off
Ts 2Ts
DTs (1-D)Ts
3Ts
time
ON
OFF
0
Vin-VoV
-Vo
time
0
A
i1
i2
1
2∆ 𝐼 𝐿∝𝐿
By volt – second balance
C1. DC-DC power choke
55
, so the duty ratio D=0.5. The switching period (two switches in half-bridge configuration)
Determine the Inductance L:
If (This is a design spec that must be given)
=
Why the switching frequency gets higher and higher? if , then
= Size and windings of the inductor will substantially increase
C1. DC-DC power choke
56 How to realize the inductance? Tackle it from the “sustained power/energy” concept
“Area product” this parameter links the electro-mechanical nature of a core.
: peak current : maximal current density on the wire, safety related : NOT , the maximal allowable flux density under this opwerational condition, it directly relates to the volt-second balance. : winding space means the current sustainability : core space means the voltage sustainability
C1. DC-DC power choke
57C1. 功率電感 (DC-DC power choke)
: 鐵芯繞線空間
銅線有絕緣塗層和不可利用的線間空間 代表實際上可用的面積比例典型值 :0.5 低壓電感0.25 to 0.3 離線變壓器0.05 to 0.2 高壓變壓器 ( 幾 kV)0.65 低壓銅箔型電感器
: 鐵
由 來選擇鐵芯尺寸
58
Pick EE22 ( easier for obtaining ),
CORESDIMENSIONS (mm) EFFECTIVE PARAMETERS
A B C D E F C1(mm-1) Le(mm) Ae(mm2) Ve(mm3) Wt(g/set)
EEL22 22.25 ± 0.30
15.26 ± 0.30 5.70 ± 0.30 5.70 ± 0.30 15.50min 11.20 ± 0.30 1.77 65.00 37.00 2405.00 11.74
Faraday’a law of induction
Turns number know now, find the gap
C1. DC-DC power choke
59
Precise doesn’t really matter.
C
AWG Dia-mm Max OD (mm) Area (mm^2) R-ohm/cm R-ohm/mm R-ohm/mm
9 2.9063 2.98 6.634E+00 2.599E-05 2.599E-05 2.599E-06 3.49086E-06
Pick AWG#9. all winding area OK!
C1. DC-DC power choke
60 Core type and winding are determined, now need to select the core material to work normally under the frequency. Bmax should be as high as possible (1st), Pv minimal (2nd), efficiency high (by the trade-off with $$)
The material can affect all the above design choices. In DC-DC choke design, the inductance is set by or , i.e., with DC content
HHrev
ACHB
µµ
0
1
)
The upper limit of also is material related.
Note : most of Hdc will drop across the gap, but the H across the core still follows the original BH curve
C1. DC-DC power choke
61
Reversible permeability at different operating points
C1. DC-DC power choke
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ITEM FINISHED PRODUCT
+ -A 10.40 0.15 0.20B 5.30 max C 8.85 0.10 0.15D 4.40 0.10 0.10E 0.80 0.10 0.10F 2.95 0.10 0.05H 8.05 0.15 0.15K 8.35 0.15 0.15T 2.15 0.10 0.05 A1 10.40 0.15 0.20C1 8.85 0.10 0.15I 2.00 0.05 0.05
Real complaint:
C1. DC-DC power choke –failure example
63
SPEC nH DC-Bias nH DC-Bias nH DC-Bias nH DC-Bias270.00 (56A) 270.00 (56A) 270.00 (56A) 270.00 (56A)
Usl 291.60 291.60 291.60 291.60 Lsl 248.40 190nH
Min 248.40 190nHMin 248.40 190nH
Min 248.40 190nHMin
Test cond. 100KHz/1V 100KHz/1Vgap 0.084mm 0.088mm 0.084mm 0.088mm
Process C/H ground, T/I ground C/H ground, T/I not groundCritical C:8.80~8.85,T: 2.14~2.2 C:8.80~8.85,T: 2.41~2.44
1 283.0 153.0 271.0 212.0 271.2 198.9 269.9 210.1 2 279.0 196.0 268.0 216.0 270.9 208.3 269.1 212.0 3 283.0 155.0 265.0 210.0 275.3 197.1 267.9 211.0 4 283.0 159.0 267.0 205.0 273.5 209.3 269.3 215.0 5 281.0 174.0 260.0 214.0 274.9 198.0 272.0 206.9 6 283.0 178.0 261.0 214.0 276.0 203.0 272.7 208.0 7 285.0 165.0 266.0 204.0 274.3 216.0 271.9 215.0 8 278.0 182.0 264.0 215.0 275.3 198.6 267.4 210.0 9 283.0 156.0 274.0 200.0 276.8 200.7 270.0 206.0
10 282.0 167.0 276.0 203.3 270.2 210.4 Max 285.0 196.0 274.0 216.0 276.8 216.0 272.7 215.0 Min 278.0 153.0 260.0 200.0 270.9 197.1 267.4 206.0
Mean 282.0 168.5 266.2 210.0 274.4 203.3 270.0 210.4
C1. DC-DC power choke –failure example
64 “Soft Ferrite” is not soft at all. Skipping the tedious calculation, it has proven that by only adding extra 4um gap, the Bmax on the core dropped from 407mT (H=76A/m) to 389mT(H=69A/m), this tiny 20mT means the difference between pass and fail ! Note that 56Adc generates H=3800A/m, but most of Hdc is dropped across the gap, only 76 or 69A/m is on the core.
C1. DC-DC power choke –failure example
65
B-H curve of no gap
B-H curve of with gap
By , the H drop on the core is still the same as the material B-H,excess H is shared by the air gap.
C1. DC-DC power choke –failure example
66
Illustration of the trade off between inductance and current handling capability of ferrite due to the limit of Hmax it allows.
C1. DC-DC power choke –failure example“Soft Ferrite” is not soft at all.
67 Uneven magnetic path in the loop will not work.
A_center 39.04 A_1 side 26.83 A_plate 19.93
This kind of geometry is no good for dc-dc choke , Ae_min section will saturate first, waste the rest core area and space.
A(mm): 15±0.4B(mm): 9.8 C(mm): 7.05±0.2D(mm): 11.7±0.3E(mm): 1.9±0.1 F(mm): 3.7±0.1
𝐴𝑠𝑖𝑑𝑒
𝐴𝑐𝑒𝑛𝑡𝑒𝑟
𝐴𝑝𝑙𝑎𝑡𝑒
C1. DC-DC power choke –failure example
68
Flyback topology and 與 waveforms ofDCM
The “transformer” (coupled inductor) stores and release energy through its magnetizing inductance Lm (by Ip & Is), and decide the converter behaviors.
Why this is “inductor” instead of transformer??One current in one winding at any instant
C2. Coupled Inductor (Flyback Transformer)
69
Popular Flyback Converter Design (3-winding)Low cost adapter
CMCDC
choke
50/60Hz AC
Vin
C2. Coupled Inductor (Flyback Transformer)
70 The design formulae are irrelevant to he magnetic component knowhow, thus are skipped here.
Comparing the coupled inductor and the DC-DC choke, their similarities and differences are
Similarity: 1. Bsat(Bmax) as high as possible2. Gap is needed for different reason. Coupled inductor uses gap for energy
management, DC-DC choke needs gap for consuming HdcDifference:3. The permeability of coupled inductor is amplitude permeability , DC-DC choke one
is differential permeability 4. As , usually Pv in general DC-DC choke is not an issue (Except the way of
Vicor P61 operation), coupled inductor is operated under the first quadrant of V-I (B-H) chart , but its to maximally drive the core, so Pvis an important factor like the case in transformer.
C2. Coupled Inductor (Flyback Transformer)
71
time
S1 on S1 off
Ts 2Ts
DTs (1-D)Ts
3Ts
time
ON
OFF
0
Vin-VoV
-Vo
time
0
A
i1
i2 ∆ 𝐼 𝐿∝𝐿
Ip Is’
DC-DC choke
Coupled inductor
time
A ∆ 𝐼 𝐿∝𝐿
C2. Coupled Inductor (Flyback Transformer)
All follow V-T balance principle
72
HHrev
ACHB
µµ
0
1
max0
1HH
aHB
µµ
∆ B
DC-DC Choke with Hdc, small Coupled Inductor, without Hdc, big
C2. Coupled Inductor (Flyback Transformer)
73 Real Design Example : a.. By below EP0714 core drawing, get Ae/Ve/Le (P4/P47 mat’l) and compare with EP7 b. What is the power rating(W) ?? c.. If power rating < 5W, feel free to redefine the core just keeping the core’s L/W/H dimensionsFrequency 100kHz, inductance 840uH (not given in the first place, means the engineer has no enough experience)
C2. Coupled Inductor (Flyback Transformer)
74
IEC60205 Magnertic Geometric Parameters
a. IEC60205 for core’s geometry factor is embedded on the right
EP0714 EP7 ui 2400 2400 uo 1.2566E-06 1.2566E-06 Ae 1.49E-05 1.03E-05 le 2.79E-02 1.57E-02 AL 1.604E-06 1.979E-060 gap N 106 106 GivenL 8.40E-04 8.40E-04 AL(g) 7.476E-08 7.476E-08 lg 2.38E-04 1.67E-04m 0.238 0.167 mm
C2. Coupled Inductor (Flyback Transformer)
75
b. Power Rating By original condition, none of two designs reach 5W power
Hdc 60 60 設計選擇Idc 3.39E-01 2.35E-01 Energy 4.8314E-05 2.3234E-05 JoulePower 4.83142813 2.3233873 Watt
C2. Coupled Inductor (Flyback Transformer)
Inductor is an “energy storing” device. The power rating actually is just the energy stored multiplied by the frequency
76
b. Power Rating By modifying the turns’ number to 120, EP0714 can sustain 6W. This is to set Hdc=60A/m (higher). Under full load, Bmax may close to saturation with lower efficiency. But it is no problem to work under 5W (with lower Hdc_max)
c. No need to do so, solved.
EP0714 EP7 N 120 120
SuggestedL 8.40E-04 8.40E-04 AL(g) 5.83333E-08 5.83333E-08 lg 3.08E-04 2.15E-04m 0.308 0.215 mmHdc 60 60 Idc 3.84E-01 2.66E-01 Energy 6.19193E-05 2.97764E-05 JoulePower 6.19 2.978Watt
WHY?
C2. Coupled Inductor (Flyback Transformer)
77
C3. SMPS transformer
Basic PrototypeIdeal Model
Flux linkage and leakageApplicable Model (1st order, winding capacitance ignored)
78
Wire intrinsic inductance and leakage
Core nature defined by B-H curve
𝐵𝑚=1/𝐿𝑚
𝐺𝑐=1/𝑅𝑐
C3. SMPS transformer
79 From ideal model, it is seen that so the efficiency can be100%. But this is impossible as current needs passing to build up the induced voltage to create the “transformer” action
When all electrical parameters determined, like DC-DC choke, the transformer core is determined by area product Ap, to have the suitable geometry for electro-magnetic conversion.𝑺𝒎𝒂𝒙=𝑿𝟏 𝑓 𝑟𝑒𝑞𝑘𝑐𝑢 𝐽𝑚𝑎𝑥 𝐵𝑚𝑎𝑥 𝐴𝑒 A𝑤 : maximal power,
: power coefficient for different excitation and core type
C3. SMPS transformer
80
EE core for example, the Ae is uneven along the flux path. The center post has Ae_min to yield a larger winding space.
To optimize , cores for transformer usually has sectionalized Ae
C3. SMPS transformer
81
If even Ae is required, the EE core will look like the left figure
The Ae obtained by IEC60205 tends to overestimate the transformer’s power handling capability.
In transformer design, the Ac used must be Ae_min for power calculation
In this way, Ap=Ac x Aw cannot be maximize.
C3. SMPS transformer
•Turns:EE5: 22 : 22EP5: 28 : 28
•I have different cores:But with some I could reach the inductance with some not and also I could not reach the current with all of them!!
82 Real example: Engineers forgot to look at the basics.
EE5 or EP5 core Inductance: 350 µH (between PIN 2 and PIN 3), 100kHz, 100mV,
8mA DCBias Saturation current: approximately 2 A DC (drop of 20%) Rated current of course at least the same Operating frequency: 1 – 125 kHz Application: Transformer for LAN application
A121 EP5 N42 EP5 A10 EE5 A07 EE5
Of Course NOT!
C3. SMPS transformer
83 Geometric facts of EE5 and EP5
This is a telecom transformer with POE (Power Over Ethernet) requirement.To have 350uH with 11 turns on EE5 and 14 turns on EP, the permeability ui must be the value shown belowi.e., no gap allowed
EE5 EP5Ae 2.66E-06 3.00E-06le 1.25E-02 9.70E-03uo 1.25664E-06 1.25664E-06N 11 14L 3.50E-04 3.50E-04AL 2.89256E-06 2.89256E-06ur 10817 7443
C3. SMPS transformer
84 Under no gap situation, when 1Adc flows through one winding, (center-tapped for split the 2A)
for EE5
for EP5 Core is saturated like air!!
P4 B-H Curve
C3. SMPS transformer
Only when Hmax (<150A/m) , there is or permeability , over it the core goes to saturation and no usable inductance for SMPS
Bsat= 520mT obtained at H =1200A/m, just for brag!
For ferrites, only this short portion is good for SMPS/filtering application
85 Winding technics and way of copper’s layout is the key to the success of inductor and transformer. This is also one of the factors that why magnetic component design is still a case by case issue. Good wiring can evenly distribute H can reduce leakage and noise, also can reduce iron and copper losses.
C. Power Choke and Transformer
86
C. Power Choke and Transformer Winding technics and way of copper’s layout is the key to the success of inductor and transformer. This is also one of the factors that why magnetic component design is still a case by case issue. Good wiring can evenly distribute H can reduce leakage and noise, also can reduce iron and copper losses.
Minimal copper losses can be obtained through careful layout and wire type selection
87
4. Open Discussions
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