ece 497 js lecture -07 planar transmission linesjsa.ece.illinois.edu/ece497js/lect_09.pdf · title:...
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1Copyright © by Jose E. Schutt-Aine , All Rights ReservedECE 497-JS, Spring 2004
ECE 497 JS Lecture -07Planar Transmission Lines
Spring 2004
Jose E. Schutt-AineElectrical & Computer Engineering
University of [email protected]
2Copyright © by Jose E. Schutt-Aine , All Rights ReservedECE 497-JS, Spring 2004
ε
Microstrip
2119.9 ln 4 16 22( 1)o
r
h hZw wε
= + + +
2
2
119.9 ln(4) ln( /16) 12 22
1 + ln ln 0.942 2 2
ro
rr
r
r
w eZh
e wh
π π επ π εε
ε ππε
−= + +
+ + +
w/h < 3.3
w/h > 3.3
3Copyright © by Jose E. Schutt-Aine , All Rights ReservedECE 497-JS, Spring 2004
1 2 3
31 1 211 12 13
VI V VC C Cz t t t
∂∂ ∂ ∂∂ ∂ ∂ ∂
− = + +
32 1 221 22 23
VI V VC C Cz t t t
∂∂ ∂ ∂∂ ∂ ∂ ∂
− = + +
3 31 231 32 33
I VV VC C Cz t t t
∂ ∂∂ ∂∂ ∂ ∂ ∂
− = + +
31 1 211 12 13
IV I IL L Lz t t t
∂∂ ∂ ∂∂ ∂ ∂ ∂
− = + +
32 1 221 22 23
IV I IL L Lz t t t
∂∂ ∂ ∂∂ ∂ ∂ ∂
− = + +
3 31 231 32 33
V II IL L Lz t t t
∂ ∂∂ ∂∂ ∂ ∂ ∂
− = + +
Three-Line Microstrip
4Copyright © by Jose E. Schutt-Aine , All Rights ReservedECE 497-JS, Spring 2004
11 13( )V IL Lz tα α∂ ∂
∂ ∂− = −
11 13( )I VC Cz tα α∂ ∂
∂ ∂− = −
Subtract (1c) from (1a) and (2c) from (2a), we get
This defines the Alpha mode with:
1 3V V Vα = − 1 3I I Iα = −and
The wave impedance of that mode is:
11 13
11 13
L LZC Cα
−=
−
and the velocity is( )( )11 13 11 13
1uL L C C
α =− −
Three-Line – Alpha Mode
5Copyright © by Jose E. Schutt-Aine , All Rights ReservedECE 497-JS, Spring 2004
In order to determine the next mode, assume that
1 2 3V V V Vβ β= + +
1 2 3I I I Iβ β= + +
( ) ( ) ( ) 31 211 21 31 12 22 32 13 23 33
V II IL L L L L L L L Lz t t tβ∂ ∂∂ ∂β β β
∂ ∂ ∂ ∂− = + + + + + + + +
( ) ( ) ( ) 31 211 21 31 12 22 32 13 23 33
I VV VC C C C C C C C Cz t t tβ∂ ∂∂ ∂β β β
∂ ∂ ∂ ∂− = + + + + + + + +
By reciprocity L32 = L23, L21 = L12, L13 = L31
By symmetry, L12 = L23
Also by approximation, L22 ≈ L11, L11+L13 ≈ L11
Three-Line – Modal Decomposition
6Copyright © by Jose E. Schutt-Aine , All Rights ReservedECE 497-JS, Spring 2004
( ) ( )31 211 12 13 12 112
V II IL L L L Lz t t tβ∂ ∂∂ ∂β β
∂ ∂ ∂ ∂ − = + + + + +
In order to balance the right-hand side into Iβ, we need to have
( ) ( ) ( )12 11 2 11 12 13 2 11 12 22L L I L L L I L L Iβ β β β β+ = + + ≈ +
212 122L Lβ=
or 2β = ±
Therefore the other two modes are defined as
The Beta mode with
Three-Line – Modal Decomposition
7Copyright © by Jose E. Schutt-Aine , All Rights ReservedECE 497-JS, Spring 2004
The Beta mode with
1 2 32V V V Vβ = + +
1 2 32I I I Iβ = + +
The characteristic impedance of the Beta mode is:
11 12 13
11 12 13
22
L L LZC C Cβ
+ +=
+ +
and propagation velocity of the Beta mode is
( )( )11 12 13 11 12 13
1
2 2u
L L L C C Cβ =
+ + + +
Three-Line – Beta Mode
8Copyright © by Jose E. Schutt-Aine , All Rights ReservedECE 497-JS, Spring 2004
The Delta mode is defined such that
1 2 32V V V Vδ = − +
1 2 32I I I Iδ = − +
The characteristic impedance of the Delta mode is
11 12 13
11 12 13
22
L L LZC C Cδ
− +=
− +
The propagation velocity of the Delta mode is:
( )( )11 12 13 11 12 13
1
2 2u
L L L C C Cδ =
− + − +
Three-Line – Delta Mode
9Copyright © by Jose E. Schutt-Aine , All Rights ReservedECE 497-JS, Spring 2004
1 0 1
1 2 1
1 2 1
E
−
= −
1 2 3
Alpha modeBeta mode*
Delta mode*
Symmetric 3-Line Microstrip
In summary: we have 3 modes for the 3-line system
*neglecting coupling between nonadjacent lines
10Copyright © by Jose E. Schutt-Aine , All Rights ReservedECE 497-JS, Spring 2004
1 2 3
εr = 4.3
113 17 5( / ) 16 53 16
5 17 113C pF m
=
346 162 67( / ) 152 683 152
67 162 346L nH m
=
0.45 0.12 0.450.5 0 0.50.45 0.87 0.45
E = − − −
0.44 0.49 0.440.5 0 0.50.10 0.88 0.10
H = − − −
Coplanar Waveguide
11Copyright © by Jose E. Schutt-Aine , All Rights ReservedECE 497-JS, Spring 2004
73 0 0( ) 0 48 0
0 0 94mZ
Ω =
56 23 8( ) 22 119 22
8 23 56cZ
Ω =
0.15 0 0( / ) 0 0.17 0
0 0 0.18pv m ns
=
1 2 3
εr = 4.3
Coplanar Waveguide
12Copyright © by Jose E. Schutt-Aine , All Rights ReservedECE 497-JS, Spring 2004
WS' S'WS
εrh
2Sk
S W=
+
( ) : Complete Elliptic Integral of the first kindK k
'( ) ( ')K k K k=
2 1/ 2' (1 )k k= −
30 '( ) (ohm)( )1
2
ocpr
K kZK k
πε
=+
1/ 22
1cpr
v cε
= +
Coplanar Waveguide
13Copyright © by Jose E. Schutt-Aine , All Rights ReservedECE 497-JS, Spring 2004
S WW
εrh
120 '( ) (ohm)( )1
2
ocsr
K kZK k
πε
=+
Coplanar Strips
14Copyright © by Jose E. Schutt-Aine , All Rights ReservedECE 497-JS, Spring 2004
Characteristic Microstrip Coplanar Wguide Coplanar strips
eeff* ~6.5 ~5 ~5
Power handling High Medium Medium
Radiation loss Low Medium Medium
Unloaded Q High Medium Low or High
Dispersion Small Medium Medium
Mounting (shunt) Hard Easy Easy
Mounting (series) Easy Easy Easy
* Assuming εr=10 and h=0.025 inch
Qualitative Comparison
15Copyright © by Jose E. Schutt-Aine , All Rights ReservedECE 497-JS, Spring 2004
3-Line Matching Network
• Extend matching network synthesis to multiconductor transmission line (MTL) systems, specifically coupled microstrip
• Characterize MTL systems by their “normal mode parameters”– Mode configurations– Propagation constants– Characteristic impedance matrices
16Copyright © by Jose E. Schutt-Aine , All Rights ReservedECE 497-JS, Spring 2004
Longitudinal Immittance Matrix Functions (LIMFs)
• Given terminations, the immittance matrices are expressed as “input”longitudinal functions looking toward the load
m,c m,cin,out
m,c m,cin,out in,out
, ,
,
ΓS
Y Z
17Copyright © by Jose E. Schutt-Aine , All Rights ReservedECE 497-JS, Spring 2004
Calibration Methods1st order calibration: 6 distinct TRL calibrations were required
to deembed the fan-in and fan-out sections 2nd order calibration: 1 multimode TRL calibration required to
deembed all fan-ins and fan-outs
Multiconductor transmission line matching network device under test
18Copyright © by Jose E. Schutt-Aine , All Rights ReservedECE 497-JS, Spring 2004
Bias Networks and Multiline/Multimode TRL
• Self-biasing for DC power done using air bridges
• Regulator circuit may be built on board with surface mount/chip components
• Calibration must include all modes and allow for the 6-port discontinuity S-parameter measurement
Proposed calibration fixture for transistor amplifier device discontinuity with self-biasing network
19Copyright © by Jose E. Schutt-Aine , All Rights ReservedECE 497-JS, Spring 2004
3-line Transistor Amplifier
The general amplifier structure with generic matching networks
Note that a transistor seating hole may be present for convenience, but is not necessary
Photograph of a three-line transistor amplifier autobiased w/o matching networks
20Copyright © by Jose E. Schutt-Aine , All Rights ReservedECE 497-JS, Spring 2004
Transistor Amplifier Matching
S-parameter comparison between unmatched and matched three-line amplifier. Dotted line - unmatched; dashed line -matched. Design frequency: 3.1 GHz.
Matching• 2 - 0.8 pF chip cap.• 2 - 0.4 pF chip cap.
Gains• 3.38 dB @ 3.1 GHz
m=5.14 / um= 1.76• 6.22 dB @ 3.22 GHz
m=6.54 / um= 0.32
21Copyright © by Jose E. Schutt-Aine , All Rights ReservedECE 497-JS, Spring 2004
2p
h
w
α
dielectric
ground
signal strip
V Transmission Line
22Copyright © by Jose E. Schutt-Aine , All Rights ReservedECE 497-JS, Spring 2004
0
50
100
150
200
250
0 0.1 0.2 0.3 0.4 0.5 0.6w/h
CHARACTERISTIC IMPEDANCE
30º37.5º45º52.5º
60ºMicrostrip
0.7 0.8 0.9 1
Zo (o
hms)
Calculated values of the characteristic impedance for a single-line v-strip structure as a function of width-to-height ratio w/h. The relative dielectric constant is εr = 2.55.
V-Line Characteristic Impedance
23Copyright © by Jose E. Schutt-Aine , All Rights ReservedECE 497-JS, Spring 2004
1.8
1.85
1.9
1.95
2
2.05
2.1
2.15
2.2
0 0.1 0.2 0.3 0.4 0.5 0.6
w/h
EFFECTIVE PERMITTIVITY
30º
37.5º
45º
52.5º
60º
Microstrip
0.7 0.8 0.9 1
Effe
ctiv
e R
elat
ive
Die
lect
ric C
onst
ant
Calculated values of the effective relative dielectric constant for a single-line v-strip structure as a function of width-to-height ratio w/h. The relative dielectric constant is εr = 2.55
V-Line – Effective Permittivity
24Copyright © by Jose E. Schutt-Aine , All Rights ReservedECE 497-JS, Spring 2004
h
y
x
Region 2
Region 3
Region 4
Region 6
Region 1
Region 5
2pw
dielectricground surface
signal strip
s
Three-Line – V Transmission Line
25Copyright © by Jose E. Schutt-Aine , All Rights ReservedECE 497-JS, Spring 2004
74.00 -0.97 -0.23C (pF/m) = -0.97 74.07 -0.97
-0.23 -0.97 74.00
425.84 20.35 7.00L (nH/m) = 20.36 422.85 20.36
7.00 20.35 425.84
52.49 -5.90 -0.57C (pF/m) = -5.90 53.27 -5.90
-0.57 -5.90 52.49
609.74 113.46 41.79L (nH/m) = 113.54 607.67 113.54
41.79 113.46 609.74
Microstrip V-line
Comparison of the inductance and capacitance matricesbetween a three-line v-line and microstrip structures. The parameters are p/h = 0.8 mils, w/h = 0.6 and εr = 4.0.
h
y
x
Region 2
Region 3
Region 4
Region 6
Region 1
Region 5
2pw
dielectricground surface
signal strip
s1 2 3
V-Line and Microstrip
26Copyright © by Jose E. Schutt-Aine , All Rights ReservedECE 497-JS, Spring 2004
0
50
100
150
200
250
300
350
0 0.2 0.4 0.6 0.8 1 1.2s/h
Mutual Inductance
V-linemicrostrip
Lm
(nH
/m)
0
5
10
15
20
25
30
35
40
0 0.2 0.4 0.6 0.8 1 1.2s/h
Mutual Capacitance
V-linemicrostrip
Cm
(pF/
m)
Plot of mutual inductance (top) and mutual capacitance (bottom) versus spacing-to-height ratiofor v-line and microstrip configurations. The parameters are w/h = 0.24, εr = 4.0.
V-Line: Coupling Coefficients
27Copyright © by Jose E. Schutt-Aine , All Rights ReservedECE 497-JS, Spring 2004
0
0.1
0.2
0.3
0.4
0.5
0.6
0 0.2 0.4 0.6 0.8 1 1.2s/h
Coupling Coefficient
V-linemicrostrip
Kv
Plot of the coupling coefficient versus spacing-to-height ratio for v-line and microstrip configurations. The parameters are w/h = 0.24, εr = 4.0.
V-Line vs Microstrip: Coupling Coefficients
28Copyright © by Jose E. Schutt-Aine , All Rights ReservedECE 497-JS, Spring 2004
0.5
0.6
0.7
0.8
0.9
1
1 3 5 7 9 11 13 15 17
microstrip
V-60
V-30
Frequency (GHz)
Linea
r Atte
nua ti
on
Propagation Function
2p
h
w
α
dielectric
ground
signal strip
Advantages of V Line* Higher bandwidth
* Lower crosstalk
* Better transition
ground reference
ground reference
dielectric
substrate
signal strip
Advantages of V-Line