[ieee 2011 norchip - lund, sweden (2011.11.14-2011.11.15)] 2011 norchip - low power programmable...
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Low Power Programmable Frequency Divider for IEEE 802.15.4a
Standard
Denys Martynenko, Gunter Fischer, Oleksiy Klymenko
IHP, Frankfurt (Oder), 1m Technologiepark 25, Germany
Abstract - This paper presents a frequency divider with a programmable division ratio between 208 and 320 intended for the standard IEEE 802.15.4a. The divider is based on high speed, low power, triple modulus prescalers. The wide division range is achieved by cascading these programmable prescalers. Each prescaler includes a phase selector and an ECL D-flip-flop which acts as a divider by 2. The triple operation of the prescaler is achieved by switching between different output phases of the D-flip-flop in the positive direction from 00 to 2700 and to the negative direction from 270° to 0°. In addition, a clock of 499.2 MHz with 50% duty cycle is available independent of the selected communication channel. The proposed divider has been evaluated for a SiGe BiCMOS technology and a maximum simulated input frequency of at least 13.5 GHz has been achieved.
Index Terms - Low power programmable frequency divider, prescaler, analog multiplexer.
I. INTRODUCTION
The commercial interest in short-range wireless
communication systems has strongly increased in the last
years. These systems become important due to their
relation with the future vision of achieving a ubiquitous
communication. Recently introduced UWB technology
shows a potential to fulfill technical and economical
requirements and to provide necessary services for such a
vision [I]. The IEEE 802.15.4a standard has been
developed based on the UWB technology. This standard
provides the physical layer for ultra-low complexity, ultra
low power, and ultra-low cost UWB devices [2].
The direct conversion front-end architecture is often
chosen as a good candidate for implementing the impulse
radio system in accordance with the IEEE 802.15.4a
standard due to its robustness and flexibility. The
frequency synthesizer (FS) is a basic building block of
many direct conversion UWB transceiver architectures. It
provides the center frequencies for 11 channels (low and
high UWB bands) and 499.2 MHz clocks for the IEEE
802.15.4a standard transceiver. Since a clock of 499.2
MHz has to be provided for all communication channels,
the multi modulus division has to be done at the high
frequency domain and the fixed division has to be moved
into the low frequency domain. All this makes the low
power design of the programmable frequency divider very
challenging.
978-1-4577-0516-8/11/$26.00 ©2011 IEEE
Several programmable high frequency dividers have
been already presented in the literature. For instance, in [3]
and [4] the authors proposed a programmable high
frequency divider architecture which is based on dual
modulus prescalers. Each of them has the same circuit
implementation, and the power dissipation of the dual
modulus prescaler is scalable with its input frequency.
However, each prescaler consists of four D latches and
additional logic and foresees the synchronous operation.
This increases the complexity of the design and raises the
overall divider power dissipation. Another solution, which
improves the power dissipation and speed of the divider, is
presented in [5] and [6]. The authors utilized a
programmable divider architecture which is based on the
fast dual-modulus prescaler. The proposed dual-modulus
prescaler uses a technique which enables the limitation of
its high-speed section to only one divide by two flip-flop.
Moreover, the control of the prescaler modes is shifted
into the low frequency domain and correspondently, the
power dissipation of the complete divider is strongly
decreased. Unfortunately, in those divider architectures,
the multi-modulus division operation is shifted in the low
frequency domain and high frequency clock of 499.2 MHz
could not be generated for each of the channels as it is
foreseen by the standard.
In this paper a low power programmable divider
architecture which provides 11 division ratios and 499.2
MHz clock for all communication channels of the IEEE
802.l5.4a standard is presented.
II. PROGRAMMABLE DIVIDER ARCHITECTURE
The block diagram of the proposed programmable
frequency divider is shown in Fig. l. The architecture
consists of high-speed EeL divide by two stages and phase
selectors (high frequency parts), ECL to CMOS converter,
CMOS divide by two stages and multi modulus CMOS
control logic (low frequency part). In order to achieve a
clock of 499.2 MHz for each of the communication
channels (IEEE 802.15.4a), the multi modulus high
frequency part of the divider is designed as a cascade of
the fast triple modulus prescalers and provides the division
range from l3 to 20. Further division is applied in the low
frequency domain with a single modulus divider by 16.
:== __ =-__ = __ =_-.HighTrequency part ---- 1 Low frequency part
I
L
I I I I I I I I I I I I I I
I I I I I : Prescaler : L _____ __________________ 1
Figure I. The block diagram of the programmable divider
D+ 1+ F+ D· I. F· MIS Q
�� Q-
F+/2 F·/2
D+ 1+ � Ph. D+ 1+ D· I. F 1 /4 , sel D· I. MIS Q ::;; F/4 5 MIS Q
• • •
�� Q _ FQ/4 .Ii �� Q_
-0 -0
Control si nal
Control F+/N
block F·/N
Figure 2. The block diagram of the conventional dual
modulus prescaler architecture
Figure 3. The principle of the N+ I operation above, and
N-l operation below
A. ECL divide by two stage and phase selector
The IEEE 802.15.4a standard foresees the
communication frequency range between 3.1 GHz and
10.6 GHz. The communication frequency range consists of
high and low UWB frequency bands, which are divided
into 11 channels. Additionally, the standard requires an
internal clock of 499.2 MHz for each of the channels.
The frequency divider is designed for 0.25 �m BiCMOS
process of IHP [7]. The CMOS part of the process allows
building the digital circuits with a clock slightly higher
than l.0 GHz. Therefore, the first four dividers by two are
499.2 MHz
I
__ __ __ __ __ --.J __
implemented with the high-speed bipolar Emitter Coupled
Logic (ECL). The ECL divide by two stage uses the
conventional master-slave architecture. This architecture is
intensively discussed in the literature [4]-[5] and will not
be described in this paper in detail.
The phase selector consists of four differential
amplifiers with switchable current sources. Each input of
the amplifiers is connected to one of the four outputs of
the ECL divider by two, as it is shown in Fig. 2.
B. Conventional and exploited NIN±l prescalers
The conventional NIN+ 1 prescaler is shown in Fig. 2.
The prescaler realization is similar to the described in [5].
The differential input signal (F+, F-) is fed in to the first
ECL divider by 2 which is connected in the master/slave
configuration. The resulting signal is ones again divided
by 2. The second divider provides, at the output, signals as
follows: differential signal of the master (1+, 1-) and
differential signal of the slave (Q+, Q-). When the control
signal is constant, the phase selector is in the passive mode
and one of the two differential signals bypasses the phase
selector and goes straight into the next ECL divider by
two. As a result, the prescaler divides the input frequency
(F) by 4. When the control signal changes its state, the
phase selector joins the actual signal F(I)/4 with 90°
delayed signal F(Q)/4. In other words, the signal with the
duration of 4*To will increase by To. Correspondently, the
period of the signal at the prescaler output will increase by
To (Fig. 3). As a result, the prescaler divides the input
frequency by 5, ones per control signal period.
The principle of the prescaler has been further exploited
in this work in order to achieve N -1 operation mode,
without introducing any additional high-speed circuitry.
The difference between the N+l and N-l operation modes
lies in the different method of phase selection. Instead of
rotating the phase in positive direction from 0° to 270°, the
phase is rotated in negative direction from 270° to 0°. In
this case, the F/4 signal will be delayed by -90°. In other
words, the signal with the duration of 4*T 0 will decrease
by To. Correspondently, the period of the signal at the prescaler output will decrease by To (Fig. 3). As a result, the prescaler divides the input frequency by 3, ones per control signal period.
,oo,� :: § � §�B�� After the shift
registers
After the control
impulses former
After the control
impulses distributor
2 shift Control 3 control registers
Figure 4. The generation of the control impulses.
C. High frequency part of the programmable divider
The divider has to provide 11 division ratios and a clock of 499.2 MHz for all communication channels in order to satisfy the requirements of the IEEE 802.15.4a standard. As it was already mentioned, the multi modulus division is shifted into the high frequency domain and provided by the high frequency divider part. The programmable division range is realized as a cascade of the triple modulus prescalers. Indeed, the placement of the prescalers one after another allows obtaining control over multiple division ratios such as NIN±I, NIN±2, NIN±4 and so on, with respect to the input frequency (F). The cascade of mentioned prescalers provides the division range between:
• minimum division ratio 2n+2 - (2n -1) • maximum division ratio 2ll+2 + (2ll -I)
where n is number of the prescalers (phase selector and the ECL divider). Unfortunately, with the divider architecture which foresees implementing minimum two dividers by two in front of the first prescaler, it is not possible to achieve the clock of the 499.2 MHz for all communication channels, as it is required by the standard. Therefore, in the proposed architecture, the first prescaler is placed after the first divider by two (Fig. 1). However, in order to provide the NIN±1 modes in this configuration,
the phase rotation in the phase selector has to be done twice per 499.2 MHz period. New divider architecture allows achieving the division ratios 2/2± 1 already after the first prescaler, the division ratios 4/4±2 after the second prescaler and so on. In this case, the cascade of the NIN±1 prescalers allows the division range between:
• minimum division ratio 2ll+1 _ (2n_l) • maximum division ratio 2n+1+ (2n_l)
The new high frequency part includes three prescalers and one ECL divider by two. This provides the division ratio from 9 to 23 with the step size of 1 and a clock of 499.2 MHz for each communication channel of the IEEE 802.15.4a standard. Another important advantage of this approach is the assurance of the clock of 499.2 MHz with 50% duty cycle. The control of triple modulus prescalers requires the design of a sophisticated control block. Nevertheless, all requirements of the IEEE 802.15.4a standards concerning the divider will be satisfied.
Additionally, the optimum configuration of the division ratios of the prescalers is improving the power dissipation of the complete divider chain. For example, the divide by 23 configuration is the most relaxed one with respect to the speed of the prescalers, because the frequency is decreased at least twice from stage to stage. The divide by 9 configuration is the most difficult one concerning the speed of the prescalers, because all prescalers operate in the N -1 mode and the first prescaler has to operate with the same speed as the first divider by two, at least ones per control signal period. However, the IEEE standard requires the division ratios between 13 and 20 and these division ratios could be achieved by different ways. For instance, the division ratio 13 could be obtained as 16-2-1 or as 16-4+l. The second configuration is much more beneficial from the power dissipation point of view, because it does not require the operation of the first prescaler in the N-I mode. Therefore, the power consumption of the first prescaler can be reduced 35% -40% with respect to the first divider by two without performance degradation of the complete divider chain. Similar combinations for the rest of the division ratios can be found without using the first prescaler in N-l operation mode.
D. Pre scalers control block
The place of the prescalers control block in the divider chain is very critical. The control block has to provide control impulses twice per 1/499.2 MHz for each of the phase selector individually. Moreover, the power dissipation of the control block has to be low. In the presented architecture, the control block is placed in the divider chain, after the ECL to CMOS converter and
designed with low power CMOS logic. The core of the
control block consists of two shift registers which are
clocked by the different phases of the 499.2 MHz input
signal (0° and IS00). Each of the shift register provides
four impulses with the duration of 2ns. The former block
processes those impulses and forms eight control impulses
with the duration of Ins in order to rotate the phase in the
phase selector twice per 499.2 MHz.
Additionally, the control block includes the start up
circuit and three control impulses distributors, one per
phase selector. The start up circuit insures that the
complete divider chain starts to operate before the first
phase rotation event happens. The distributors provide the
control impulses to the phase selectors. It is important to
mention that the control impulses have to be completely
overlap each other; otherwise the proper operation of the
phase selector will be not possible. For this reason, the
raising edge of the control impulse has to be sharp and the
falling edge has to be smooth. The generation of the
control impulses is shown in Fig. 4.
E. Low frequency divider chain
The low frequency divider chain consists of four CMOS
divide by two cells. They are implemented in order to
divide 499.2 MHz down to 31.2 MHz. Frequency of 31.2
MHz is recommended by the IEEE S02.15.4a standard as
a reference frequency for the complete system. The CMOS
divider by two is designed as dynamic CMOS D flip-flop
similar to [5].
III. SIMULATION RESULTS
The programmable frequency divider is designed using
0.25 11m BiCMOS SiGe technology of IHP. The
simulation has been done for the worst case corners and
with the temperature of 125° C. All required division ratios
between 20S and 320 with the step size of 16 are obtained.
The divider chain provides a clock of 499.2 MHz with
50% duty cycle for all communication channels of the
IEEE S02.15.4a standard. The maximum simulated input
frequency for minimum possible division ratio (the most
stringent condition) results in l3.5 GHz. The main input
frequency limitation factor is the speed of the CMOS
control block. The speed of the control block seems to be
problematic to improve due to the technological limitation
of the CMOS devices. The performance of the
programmable divider chain is summarized in table I.
Table I The performance of the programmable frequency
divider
Input frequency range 6.0 GHz .. I 0.6 GHz
High frequency clock 499.2 MHz
Output frequency 3l.2 MHz
Division ratio 20S .. 320
Step size 16
Supply voltage 2.6V
Current consumption
- high freq uency part 5.06 mA
- control block 1.02 rnA
- ECL to CMOS converter 1.06 rnA
- CMOS divider by 16 0.45 mA
- total 7.59 rnA
VII. CONCLUSION
The programmable frequency divider which provides all
required division ratios and a clock of 499.2 MHz with
50% duty cycle in accordance with the IEEE S02.15.4a
standard has been designed and simulated. This divider is
based on the cascade of the high frequency triple modulus
prescalers. The control of the prescalers is shifted into the
low frequency domain. Therefore, the power consumption
of the complete programmable divider is strongly
decreased without degradation of the speed performance.
REFERENCES
[1] C. Chong, F. Watanabe, and H. Inamura, "Potential of UWB technology for the next generation wireless communication," ISSSTA, pp. 422 - 429, Aug. 2006.
[2] IEEE Std. S02.15.4a-2007. [3] S. Vaucher, I. Ferencic, M. Locher, S. Sedvallson and
others "A family of low-power truly modular programmable dividers in standard 0.35-/lm CMOS Technology," JSSC, Vol. 35, No.7, July 2000, pp. 1039-1045.
[4] M. Ray, W. Souder, M. Ratcliff, F. Dai and J. D. Irwin "A 13 GHz low power multi-modulus divider implemented in 0.13 /lm SiGe technology," SiRF, Feb. 2009, pp. 1-4.
[5] J. Craninckx and M. S. J. Steyaert, "A 1.75-GHz/3V dualmodulus divide-by-128/129 prescaler in 0.7-/lm CMOS," JSSC, Vol. 31, No.7, July 1996, pp. 890-897.
[6] N. Krishnapura and P. R. Kinget, "A 5.3-GHz programmable diver for HiPerLAN in 0.25-/lm CMOS," JSSC, Vol. 35, No.7, July 2000, pp. 1019-1024.
[7] Foundry Service of IHP,
Available: http://www.ihp-microelectronics.com