effective power/ground plane decoupling for pcbweb.mst.edu/~jfan/slides/archambeault1.pdf ·...
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Effective Power/Ground Plane Decoupling for PCB
Dr. Bruce ArchambeaultIBM Distinguished Engineer
IEEE Fellow
IBMResearch Triangle Park, NC
October 2007IEEE
October 2007 Dr. Bruce Archambeault 2
“Ground Bounce”
Power Plane Noise Control
October 2007 Dr. Bruce Archambeault 3
Power/Ground-Reference Plane Noise
• Must consider TWO Major Factors– EMC -- Reduce noise along edge of board from IC
somewhere else– Functionality -- Provide IC with sufficient charge
• Decoupling strategies are FULL of Myths– Consider the physics– Don’t forget Inductance!
October 2007 Dr. Bruce Archambeault 4
Source of Power/Ground-Reference Plane Noise
• Power requirements from IC during switching
• Critical Net currents routed through via
October 2007 Dr. Bruce Archambeault 5
Power Bus SpectrumClock Driver IDT74FCT807
October 2007 Dr. Bruce Archambeault 6
Noise Injected between Planes Due to Critical Net Through Via
Signal Via
I/O Pin/Via
30 cm
20 cm
FR4 r=4.2 Loss tan=0.02
October 2007 Dr. Bruce Archambeault 7
Transfer Function from Via to I/O PinTransfer Function From Via-to-Via
20x30cm Board
-70
-60
-50
-40
-30
-20
-10
0
1.E+08 1.E+09 1.E+10
Frequency (Hz)
Tran
sfer
Fun
ctio
n (d
B)
5 mil Seperation10 mil Seperation15 mil Seperation25 mil Seperation35 mil Seperation
October 2007 Dr. Bruce Archambeault 8
Decoupling Must be Analyzed in Different Ways for Different Functions
• EMC– Resonance big concern– Requires STEADY-STATE analysis
• Frequency Domain– Transfer function analysis
• Eliminate noise along edge of board due to ASIC/IC located far away
October 2007 Dr. Bruce Archambeault 9
Decoupling Must be Analyzed in Different Ways for Different
Functions
• Provide Charge to ASIC/IC– Requires TRANSIENT analysis– Charge will NOT travel from far corners of the
board fast enough– Local decoupling capacitors dominate– Impedance at ASIC/IC pins important
October 2007 Dr. Bruce Archambeault 10
Steady-State Analysis
• Measurements and Simulations• Test Board with Decoupling capacitors
every 1” square
October 2007 Dr. Bruce Archambeault 11
5”
1”
9”10”
1”3”
6”9”
11”12”
Figure 1
Test Board Ports
#1 #2 #3 #4 #5
#6 #7 #8 #9 #10
#11 #12 #13 #14 #15
October 2007 Dr. Bruce Archambeault 12
S21 Used for Decoupling “Goodness”
• Ratio of Power ‘out’ to power ‘in’• Better Indicator of EMI noise transmission
across board• Also used to validate simulations
October 2007 Dr. Bruce Archambeault 13
Measured S21 for 12" x 10" PC Board Between Power/Ground Planeswith No Decoupling Capacitors
(Measured Center to Corner)
-80
-70
-60
-50
-40
-30
-20
-10
0
0.0E+00 1.0E+08 2.0E+08 3.0E+08 4.0E+08 5.0E+08 6.0E+08 7.0E+08 8.0E+08 9.0E+08 1.0E+09
Frequency (Hz)
S21
(dB
)
Board Capacitance Dominates
Physical Board Size Resonances Dominate
October 2007 Dr. Bruce Archambeault 14
Test Board Decoupling Capacitor Placement for 25 .01 uf Caps
Possible CapLocation
PopulatedCapLocations
October 2007 Dr. Bruce Archambeault 15
Test Board Decoupling Capacitor Placement for 51 .01 uf Caps
Possible CapLocation
PopulatedCapLocations
October 2007 Dr. Bruce Archambeault 16
Measured S21 for 12" x 10" PC Board Between Power/Ground Planeswith Various Amounts of Decoupling Capacitors
(Measured Center to Corner)
-100
-90
-80
-70
-60
-50
-40
-30
-20
-10
0
0.0E+00 2.0E+08 4.0E+08 6.0E+08 8.0E+08 1.0E+09 1.2E+09 1.4E+09 1.6E+09 1.8E+09
Frequency (Hz)
S21
(dB
)
No Caps25 Caps50 Caps99 Caps
Measured S21 for 12" x 10" PC Board Between Power/Ground Planeswith Various Amounts of Decoupling Capacitors
(Measured Center to Corner)
-100
-90
-80
-70
-60
-50
-40
-30
-20
-10
0
0.0E+00 2.0E+08 4.0E+08 6.0E+08 8.0E+08 1.0E+09 1.2E+09 1.4E+09 1.6E+09 1.8E+09
Frequency (Hz)
S21
(dB
)
No Caps25 Caps50 Caps99 Caps
October 2007 Dr. Bruce Archambeault 17
S21 Between Port #8 and Port #1 on Test BoardWith Various Amounts of .01 uf Decoupling Capacitors
-60
-50
-40
-30
-20
-10
0
0.0E+00 2.0E+08 4.0E+08 6.0E+08 8.0E+08 1.0E+09 1.2E+09 1.4E+09 1.6E+09 1.8E+09
Frequency (Hz)
S21
(dB
)
No Caps
25 Caps
51 Caps
99 Caps
October 2007 Dr. Bruce Archambeault 18
1.00E+6 1.00E+7 1.00E+8 1.00E+9 1.00E+10
Freq (Hz)
0.1
1
10
100
1000
10000
|Z| (
Ohm
s)
0.01uF22pF0.01uF in parallel with 22pF
Cap Impedance
October 2007 Dr. Bruce Archambeault 19
Test Board Decoupling Capacitor Placement for 41 22pf Caps
(In Addition to 99 .01uf Caps)
Possible CapLocation
PopulatedCapLocations
October 2007 Dr. Bruce Archambeault 20
S21 Between Port #8 and Port #1 on Test BoardWith 99 .01 uf Decoupling Capacitors and Various Amounts of 22pf
Capacitors Added
-60
-50
-40
-30
-20
-10
0
0.0E+00 2.0E+08 4.0E+08 6.0E+08 8.0E+08 1.0E+09 1.2E+09 1.4E+09 1.6E+09 1.8E+09
Frequency (Hz)
S21
(dB
)
9 22pf Caps17 22pf Caps21 22pf Caps33 22pf Caps41 22pf Caps99 22pf Caps99 Caps
October 2007 Dr. Bruce Archambeault 21
Measured Comparison of Multiple and Single Value Decoupling Capacitor Strategies
-100
-90
-80
-70
-60
-50
-40
-30
-20
-10
0
0.0E+00 2.0E+08 4.0E+08 6.0E+08 8.0E+08 1.0E+09 1.2E+09 1.4E+09 1.6E+09 1.8E+09
Frequency (Hz)
S21
Tran
sfer
Fun
ctio
n (d
B)
No Caps99 0.01 uF Caps0.01 uF and 330 pF Caps
October 2007 Dr. Bruce Archambeault 22
Comparison of Model and Measured Datafor 10" x 12" Board
99 caps -- alternating .01uF and 330pF
-100.0
-90.0
-80.0
-70.0
-60.0
-50.0
-40.0
-30.0
-20.0
-10.0
0.0
0.0E+00 1.0E+08 2.0E+08 3.0E+08 4.0E+08 5.0E+08 6.0E+08 7.0E+08 8.0E+08 9.0E+08 1.0E+09
Frequency (Hz)
S21
(dB
)
CIAO - .01uF & 330 pF
Measured
October 2007 Dr. Bruce Archambeault 23
S21 Transfer Function for Different Value CapacitorsCenter-to-Corner10" x 12" Board
-80
-70
-60
-50
-40
-30
-20
-10
0
0.0E+00 1.0E+08 2.0E+08 3.0E+08 4.0E+08 5.0E+08 6.0E+08 7.0E+08 8.0E+08 9.0E+08 1.0E+09
Frequency (Hz)
S21
(dB
)
99 .01uF caps
99 0.1uF caps
99 0.33uF caps
99 Caps (0.01uF and 330pF)
99 2nh shorts
October 2007 Dr. Bruce Archambeault 24
Voltage Distribution @ 350 MHz.01uF and 330pF Case (Source in
Center)
October 2007 Dr. Bruce Archambeault 25
Voltage Distribution @ 750 MHz.01uF and 330pF Case (Source in
Center)
October 2007 Dr. Bruce Archambeault 26
Voltage Distribution @ 950 MHz.01uF and 330pF Case (Source in
Center)
October 2007 Dr. Bruce Archambeault 27
Decoupling Capacitor Mounting
• Keep as to planes as close to capacitor pads as possible
Height above Planes
Via Separation
Inductance Depends on Loop AREA
October 2007 Dr. Bruce Archambeault 28
Decoupling Capacitor Mounting
• Keep as to planes as close to capacitor pads as possible
CapacitorICCapacitor Connection Inductance Loop
IC Connection Inductance Loop
Plane Inductance Loop
October 2007 Dr. Bruce Archambeault 29
Via Configuration Can Change Inductance
Via
Capacitor Pads
SMT Capacitor
The “Good”
The “Bad”
The “Ugly”
Really “Ugly”
Better
Best
October 2007 Dr. Bruce Archambeault 30
Comparison of Decoupling Capacitor Impedance100 mil Between Vias & 10 mil to Planes
0.01
0.1
1
10
100
1000
1.0E+06 1.0E+07 1.0E+08 1.0E+09 1.0E+10
Frequency (Hz)
Impe
danc
e (o
hms)
1000pF
0.01uF
0.1uF
1.0uF
October 2007 Dr. Bruce Archambeault 31
Via Seperation (mils) Inductance (nH) Impedance @ 1 GHz (ohms) 20 .06 .41 40 0.21 1.3 60 0.36 2.33 80 0.5 3.1
100 0.64 4.0 150 1.0 6.23 200 1.4 8.5 300 2.1 12.69 400 2.75 17.3 500 3.5 21.7
Comparison of Decoupling Capacitor Via Separation Distance Effects
0.1 uF Capacitor10 mils
Via Separation
October 2007 Dr. Bruce Archambeault 32
Example Connection Inductance Values
2.07 nH2.4 nH4.3 nH4.2 nH0603 + 2*160mil
1.5 nH2.1 nH3.15 nH3.3 nH0603 + 2*100mil
0.8 nH1.1 nH1.74 nH2.3 nH0603 + 2*10mil
2.5 nH3.5 nH5.1 nH5.1 nH0805 + 2*160mil
2.0 nH3 nH4.3 nH4.1 nH0805 + 2*100mil
1.38 nH2 nH3.1 nH3.0 nH0805 + 2*10mil
Simple rect loop(10 mils to plane)
Complex Formula(10 mils to plane)
Simple rect loop(20 mils to
plane)
Complex Formula
(20 mils to plane)
Spacing between
Vias
Fan, Jun, Wei Cui, James L. Drewniak, Thomas Van Doren, and James L. Knighten, “Estimating the Noise Mitigating Effect of Local Decoupling in Printed Circuit Boards,” IEEE Trans. on Advanced Packaging, Vol. 25, No. 2, May 2002, pp. 154-165.
Knighten, James L., Bruce Archambeault, Jun Fan, Samuel Connor, James L. Drewniak, “PDN Design Strategies: II. Ceramic SMT Decoupling Capacitors – Does Location Matter?,” IEEE EMC Society Newsletter, Issue No. x, Winter 2006, pp. 56-67. (www.emcs.org)
Sources for complex formula:
October 2007 Dr. Bruce Archambeault 33
Transient Analysis(Time Limited)
• Provide charge to ASIC/IC• Inductance dominates impedance
– Loop area 1st order effect• Traditional analysis not accurate
enough
October 2007 Dr. Bruce Archambeault 34
switch IC loadICdriverVDC
GND
CL
VCC
Z0, vp
GND
IC loadICdriver
VCC
VCC
charge
logic 0-1
Z0, vp
shoot-thru current
IC loadICdriver
GND
VCC
0 V
discharge
logic 1-0
Z0, vp
shoot-thru current
Current in IC During Logic Transitions (CMOS)
October 2007 Dr. Bruce Archambeault 35
Typical PCB Power Delivery
GND
VCC
DC/DC converter
(Power source)
GNDVCC
IC load
VCCGND
SMT capacitors
VCCGND
IC driver VCC
GND
electrolyticcapacitor
VCC
GND
October 2007 Dr. Bruce Archambeault 36
Equivalent Circuit for Power Current Delivery to IC
switchVDC
LtraceLps
Lbulk
Cbulk
Lvia
CSMT
Cplanes
connector and wiring capacitor
leads
electrolytic capacitors
via interconnect
SMT capacitors VCC/GND
plane
IC load
PCBwiring
DC/DCconverter
October 2007 Dr. Bruce Archambeault 37
Traditional Analysis #1
• Use impedance of capacitors in parallel
Impedance to IC power/gnd pins
ESR1 ESR4ESR3ESR2
ESL1 ESL4ESL3ESL2
1uF .001uF0.01uF0. 1uF
No Effect of Distance Between Capacitors and IC Included!
October 2007 Dr. Bruce Archambeault 38
Traditional Impedance Calculation for Four Decoupling Capacitor Values
0.01
0.1
1
10
100
1000
1.00E+07 1.00E+08 1.00E+09
Frequency (Hz)
Impe
danc
e (o
hms)
.1uF
.01uF
.001uF
.0001uFAll in Parallel
October 2007 Dr. Bruce Archambeault 39
Traditional Analysis #2• Calculate loop area – Traditional loop
Inductance formulas– Which loop area? Which size conductor
Impedance to IC power/gnd pins
ESR1 ESR4ESR3ESR2
ESL1+Ld1
1uF .001uF0.01uF0. 1uF
ESL2+Ld2 ESL3+Ld3 ESL4+Ld4
Over Estimates L and Ignores Distributed Capacitance
October 2007 Dr. Bruce Archambeault 40
More Accurate Model Includes Distributed Capacitance
Distributed
capacitors
Intentional Decoupling Capacitors
Distributed
capacitors
IC Power Pin
Intentional Decoupling Capacitors
October 2007 Dr. Bruce Archambeault 41
Distributed Capacitance Schematic
Loop L
Capacitance
ESR
Distributed CapacitanceIntentional Capacitor
Source
Note: L increases as distance from source increases
Loop L
Capacitance
ESR
Distributed CapacitanceIntentional Capacitor
SourceSource
Note: L increases as distance from source increases
October 2007 Dr. Bruce Archambeault 42
Effect of Distributed Capacitance
• Can NOT be calculated/estimated using traditional capacitance equation
• Displacement current amplitude changes with position and distance from the source
October 2007 Dr. Bruce Archambeault 43
Displacement Current 500 MHz via @450 mils from
Source
October 2007 Dr. Bruce Archambeault 44
Need to Find the Real Effect of Decoupling Capacitor Distance
• Perfect decoupling capacitor is a via between planes
• FDTD simulation to find the effect of shorting via distance from source
• Vary spacing between planes, distance to via, frequency, etc
October 2007 Dr. Bruce Archambeault 45
Impedance of Shorting Via vs. Frequency Four Via Case (20 mil Seperation Between Plates)
0.1
1
10
100
1.E+08 1.E+09 1.E+10
Frequency (Hz)
Impe
danc
e (o
hms)
20mils 40mils50mils 60mils70mils 80mils90mils 100mils120mils 130mils140mils 150mils160mils 180mils200mils 220mils240mils 250mils350mils 450mils
October 2007 Dr. Bruce Archambeault 46
Impedance Result
• Linear with frequency (on log scale)• Looks like an inductance only!• Consider this inductance an Apparent
Inductance• Apparent inductance is constant with
frequency
October 2007 Dr. Bruce Archambeault 47
Apparent Inductance for One Shorting Via Case20 mil Plate Separation
0
0.2
0.4
0.6
0.8
1
1.2
1.E+08 1.E+09 1.E+1
Frequency (Hz)
Indu
ctan
ce (n
H)
50mils110mils120mils200mils250mils350mils450mils
October 2007 Dr. Bruce Archambeault 48
Formulas to Predict Apparent Inductance
)1592.02774.0()()0403.01192.0()1763.02848.0()()0447.01242.0(
)1943.02948.0()()0492.01307.0()2675.02609.0()()0654.01336.0(
+−+−=+−+−=
+−+−=+−+−=
−
−
−
−
sdistLnsLsdistLnsLsdistLnsLsdistLnsL
viafour
viathree
viatwo
viaone
s = separation between plates (mils/10)
dist = distance to via
October 2007 Dr. Bruce Archambeault 49
LapparentLIC Lcap
IC Capacitor
PowerGnd
Lapparent
ESR
Lcap + LIC
Nominal Capacitance
Source
True Impedance for Decoupling Capacitor
October 2007 Dr. Bruce Archambeault 50
Impedance Calculation with Apparent Inductancefor Four Decoupling Capacitor Values
0.01
0.1
1
10
1.E+07 1.E+08 1.E+09
Frequency (Hz)
Impe
danc
e (o
hms)
Case1
Case2Case3
Traditional Calculation
Cap Value Distance to Cap from IC Case 1 Case 2 Case 30.1 uF 800mils 1200mils 1500mils0.01 uF 600mils 900mils 1100mils0.001uF 400mils 700mils 800mils0.0001uF 200mils 400mils 400mils
October 2007 Dr. Bruce Archambeault 51
Effect of Distributed Capacitance
• Can NOT be calculated/estimated using traditional capacitance equation
• Displacement current amplitude changes with position and distance from the source
• Following examples use cavity resonance technique (EZ-PowerPlane)– Frequency Domain to compare to measurements– Time Domain using SPICE circuit from cavity
resonance analysis
October 2007 Dr. Bruce Archambeault 52
Parameters for Comparison to Measurements
• Dielectric thickness = 35 mils• Dielectric constant = 4.5, Loss tan = 0.02• Copper conductivity = 5.8 e7 S/m
October 2007 Dr. Bruce Archambeault 53
Measured vs Model (MoM) S21 for 12" x 10" PC Power/gndwith 25 .01uF caps
Position 8-to-1
-50
-40
-30
-20
-10
0
1.0E+07 1.0E+08 1.0E+09 1.0E+10
Frequency (Hz)
S21
(dB
)
No Caps - Measured
EZ-PP No Caps
October 2007 Dr. Bruce Archambeault 54
Measured vs Model (EZ-PP) S21 for 12" x 10" PC Power/gndwith 25 .01uF caps
Position 8-to-1
-100.0
-90.0
-80.0
-70.0
-60.0
-50.0
-40.0
-30.0
-20.0
-10.0
0.0
1.0E+07 1.0E+08 1.0E+09 1.0E+10
Frequency (Hz)
S21
(dB
)
Measured
EZ-PP 25 caps
October 2007 Dr. Bruce Archambeault 55
Measured vs Model (EZ-PP) S21 for 12" x 10" PC Power/gndwith 95 .01uF caps
Position 8-to-1
-100.0
-90.0
-80.0
-70.0
-60.0
-50.0
-40.0
-30.0
-20.0
-10.0
0.0
1.0E+07 1.0E+08 1.0E+09 1.0E+10
Frequency (Hz)
S21
(dB
)
95 Caps - Measured95 Caps - EZ-PP
October 2007 Dr. Bruce Archambeault 56
Impedance at Port #1Single 0.01 uF Capacitor at Various Distances (35mil Dielectric)
-40
-30
-20
-10
0
10
20
30
1.0E+07 1.0E+08 1.0E+09 1.0E+10Frequency (Hz)
Impe
danc
e (d
Boh
ms)
no caps300 mils500 mils700 mils1000 mils
October 2007 Dr. Bruce Archambeault 57
Z11 Phase Comparison as Capacitor distance Varies for 35 mils FR4ESL = 0.5nH
-2
-1.5
-1
-0.5
0
0.5
1
1.5
2
1.0E+06 1.0E+07 1.0E+08 1.0E+09
Frequency (Hz)
Phas
e (r
ad)
100 mils200 mils300 mils400 mils1000 mils2000 mils
October 2007 Dr. Bruce Archambeault 58
Impedance at Port #1Single 0.01 uF Capacitor at Various Distances (10mil Dielectric)
-50
-40
-30
-20
-10
0
10
20
1.0E+07 1.0E+08 1.0E+09 1.0E+10
Frequency (Hz)
Impe
danc
e (d
Boh
ms) no caps
300 mils500 mils700 mils1000 mils
October 2007 Dr. Bruce Archambeault 59
Cavity Resonance (EZ-PowerPlane) Equivalent Circuit for HSPICE
Lii Ljj
Lij
N00i
N01i
Nmni Nmnj
N01j
N00jC0
C0
C0
G00
G01
Gmn
L01
Lmn
Port i Port j
Port n
October 2007 Dr. Bruce Archambeault 60
Impedance Comparison (EZ-PP vs HSPICE) at Port #1Single 0.01 uF Capacitor at Various Distances (10mil Dielectric)
-50
-40
-30
-20
-10
0
10
20
1.0E+07 1.0E+08 1.0E+09 1.0E+10
Frequency (Hz)
Impe
danc
e (d
Boh
ms)
300 mils300 mils (HSPICE)1000 mils1000 mils (HSPICE)
October 2007 Dr. Bruce Archambeault 61
Current Source Pulse for Simulated IC Power/GND750 ps Rise/Fall
-0.2
0
0.2
0.4
0.6
0.8
1
1.2
0 0.5 1 1.5 2 2.5 3 3.5 4
Time (ns)
Cur
rent
(am
ps)
October 2007 Dr. Bruce Archambeault 62
Time Domain Noise Voltage Across Simulated IC Power/GND Pin (1 amp)Single Capacitor (with 2 nH) at Various Distances (Fullwave Simulation)
-1.5
-1
-0.5
0
0.5
1
1.5
2
0 0.5 1 1.5 2 2.5 3 3.5 4
Time (ns)
Leve
l (vo
lts)
750ps Rise, 35 mil planes,1uF @ 10mils750ps Rise, 35 mil planes, 1uF @ 400mils750ps Rise, 35 mil planes,1uF @ 800mils750ps Rise, 35 mil planes,1uF @ 1200mils750ps Rise, 35 mil planes,1uF @ 1600mils
October 2007 Dr. Bruce Archambeault 63
Time Domain Current through Capacitor From Simulated IC Power/GND (1 amp)Single Capacitor (with 2nH) at Various Distances
-400
-350
-300
-250
-200
-150
-100
-50
0
50
0 0.5 1 1.5 2 2.5 3 3.5 4
Time (ns)
Cur
rent
(mill
iam
ps)
750ps Rise, 35 mil planes,1uF @ 10mils750ps Rise, 35 mil planes,1uF @ 400mils750ps Rise, 35 mil planes,1uF @ 800mils750ps Rise, 35 mil planes,1uF @ 1200mils750ps Rise, 35 mil planes,1uF @ 1600mils
October 2007 Dr. Bruce Archambeault 64
Time Domain Noise Voltage Across Simulated IC Power/GND Pin (1 amp)Single Capacitor (with No L) at Various Distances
-2
-1.5
-1
-0.5
0
0.5
1
1.5
2
0 0.5 1 1.5 2 2.5 3 3.5 4
Time (ns)
Leve
l (vo
lts)
750ps Rise, 35 mil planes,1uF @ 10mils750ps Rise, 35 mil planes,1uF @ 400mils750ps Rise, 35 mil planes,1uF @ 800mils750ps Rise, 35 mil planes,1uF @ 1200mils750ps Rise, 35 mil planes,1uF @ 1600mils
October 2007 Dr. Bruce Archambeault 65
Time Domain Current through Capacitor From Simulated IC Power/GND (1 amp)Single Capacitor (with no L) at Various Distances
-1200
-1000
-800
-600
-400
-200
0
200
400
0 0.5 1 1.5 2 2.5 3 3.5 4
Time (ns)
Cur
rent
(mill
iam
ps)
750ps Rise, 35 mil planes,1uF @ 10mils750ps Rise, 35 mil planes,1uF @ 10mils750ps Rise, 35 mil planes,1uF @ 800mils750ps Rise, 35 mil planes,1uF @ 1200mils750ps Rise, 35 mil planes,1uF @ 1600mils
October 2007 Dr. Bruce Archambeault 66
Time Domain Noise Voltage Across Simulated IC Power/GND Pin (1 amp)Single Capacitor with Various Capacitor Connection Inductance
-0.4
-0.3
-0.2
-0.1
0
0.1
0.2
0.3
0.4
0.5
0.6
0 0.5 1 1.5 2 2.5 3 3.5 4 4.5
Time (ns)
Leve
l (vo
lts)
750ps Rise, 10 mil planes, 1uF @ 400mils750ps Rise, 10 mil planes, (2nH) 1uF @ 400mils750ps Rise, 10 mil planes, (1nH) 1uF @ 400mils
October 2007 Dr. Bruce Archambeault 67
Time Domain Noise Voltage Across Simulated IC Power/GND Pin (1 amp)Single Capacitor with Various Capacitor Connection Inductance
-1.5
-1
-0.5
0
0.5
1
1.5
2
0 0.5 1 1.5 2 2.5 3 3.5 4
Time (ns)
Leve
l (vo
lts)
750ps Rise, 10 mil planes, 1uF @ 400mils750ps Rise, 10 mil planes, (2nH) 1uF @ 400mils750ps Rise, 35 mil planes,1uF @ 400mils750ps Rise, 35 mil planes,(2nH) 1uF @ 400mils
October 2007 Dr. Bruce Archambeault 68
Maximum Time Domain Noise Voltage Across Simulated IC Power/GND Pin Single Capacitor at Various Distances (Fullwave Simulation)
0
0.1
0.2
0.3
0.4
0.5
0.6
0.7
0.8
0 200 400 600 800 1000 1200 1400 1600 1800
Distance (mils)
Volta
ge (v
olts
)
750 ps Rise, 10 mil planes,1uF, 2 nH750 ps Rise, 10 mil planes,1uF, 1 nH750 ps Rise, 10 mil planes,1uF, 0.5 nH750 ps Rise, 10 mil planes,1uF, No L
October 2007 Dr. Bruce Archambeault 69
Maximum Time Domain Noise Voltage Across Simulated IC Power/GND Pin Single Capacitor at Various Distances (Fullwave Simulation)
0
0.1
0.2
0.3
0.4
0.5
0.6
0.7
0.8
0 200 400 600 800 1000 1200 1400 1600 1800
Distance (mils)
Volta
ge (v
olts
)
1 ns Rise, 10 mil planes,1uF, 2 nH1 ns Rise, 10 mil planes,1uF, 1 nH1 ns Rise, 10 mil planes,1uF, 0.5 nH1 ns Rise, 10 mil planes,1uF, No L
October 2007 Dr. Bruce Archambeault 70
Maximum Time Domain Noise Voltage Across Simulated IC Power/GND Pin Single Capacitor at Various Distances (Fullwave Simulation)
0
0.2
0.4
0.6
0.8
1
1.2
1.4
1.6
1.8
0 200 400 600 800 1000 1200 1400 1600 1800
Distance (mils)
Volta
ge (v
olts
)
750 ps Rise, 35 mil planes,1uF, 2 nH
750 ps Rise, 35 mil planes,1uF, 1 nH
750 ps Rise, 35 mil planes,1uF, 0.5 nH
750 ps Rise, 35 mil planes,1uF, No L
October 2007 Dr. Bruce Archambeault 71
Maximum Time Domain Noise Voltage Across Simulated IC Power/GND Pin Single Capacitor at Various Distances (Fullwave Simulation)
0
0.2
0.4
0.6
0.8
1
1.2
1.4
1.6
0 200 400 600 800 1000 1200 1400 1600 1800
Distance (mils)
Volta
ge (v
olts
)
1 ns Rise, 35 mil planes,1uF, 2 nH1 ns Rise, 35 mil planes,1uF, No L1 ns Rise, 35 mil planes,1uF, 0.5 nH1 ns Rise, 35 mil planes,1uF, 1 nH
October 2007 Dr. Bruce Archambeault 72
Maximum Voltage vs Distance to Capacitor for 1 ns Rise/fall time0.01 uF Capacitor with 0.5 nH ESL and 30 mOhm ESR
0
0.2
0.4
0.6
0.8
1
1.2
1.4
0 200 400 600 800 1000 1200 1400 1600 1800 2000
Distance From Capacitor (mils)
Max
imum
Vol
tage
at s
ourc
e (v
olts
)
35 mil FR410 mil FR42 mil FR41 mil FR40.5 mil FR4
October 2007 Dr. Bruce Archambeault 73
So Far……• Frequency domain simulations not
optimum for charge delivery decoupling calculations (phase not considered)
• Time domain simulations using single pulse of current indicate limited capacitor location effect– Connection inductance of capacitor much
higher than inductance between planes– Charge delivered only from the planes
October 2007 Dr. Bruce Archambeault 74
Charge Depletion
• IC draws charge from planes• Capacitors will re-charge planes
– Location does matter!
October 2007 Dr. Bruce Archambeault 75
Model for Plane Recharge Investigations
Port2 Port2 (4,5)(4,5)
Port1Port1(8,7)(8,7)
a = 12a = 12
b = 10b = 10
d = 35 mild = 35 milCdec Cdec
(4.05,5)(4.05,5)
Decoupling Capacitor :C = 1uFESR = 30mOhmESL = 0.5nH
5.4=rε
DC voltage used to DC voltage used to charge the power charge the power
plane plane
VdcVdc
I inputI input
Port3 Port3 (4,4.95)(4,4.95)
Port2 Port2 (4,5)(4,5)
Port1Port1(8,7)(8,7)
a = 12a = 12
b = 10b = 10
d = 35 mild = 35 milCdec Cdec
(4.05,5)(4.05,5)
Decoupling Capacitor :C = 1uFESR = 30mOhmESL = 0.5nH
5.4=rε
DC voltage used to DC voltage used to charge the power charge the power
plane plane
VdcVdc
I inputI input
Port3 Port3 (4,4.95)(4,4.95)
Port 2 represents IC current draw
October 2007 Dr. Bruce Archambeault 76
Charge Between Planes vs.. Charge Drawn by IC
Board total charge : C*V = 3.5nF*3.3V = 11nC
Pulse charge 5A peak : I*dt/2 = (1ns*5A)/2=2.5nC
October 2007 Dr. Bruce Archambeault 77
Triangular pulses (5 Amps Peak)
October 2007 Dr. Bruce Archambeault 78
(a)
(b)
Noise Voltage from Inductive Effect of Current Draw
Current pulses too small to see charge depletion effects in this time scale
October 2007 Dr. Bruce Archambeault 79
Charge Depletion Voltage Drop
0 2 4 6 8 101
1.5
2
2.5
3
3.5
4
Time [ns]
Vpl
ane [
V]
Ls = 1nHLs = 10 nH
Ls = 50 nH
October 2007 Dr. Bruce Archambeault 80
Charge Depletion vs. Capacitor Distance
October 2007 Dr. Bruce Archambeault 81
Charge Depletion for Capacitor @ 400 mils for Various Connection Inductance
October 2007 Dr. Bruce Archambeault 82
Effect of Multiple Capacitors While Keeping Total Capacitance Constant
(power-ground pins at IC center)
12”
10”
Port1 (8,7)(Ls 50nH)
Port2 (4,5)(power pin)
εr =4.5
Decap
Ground pin1 inch
The decap locations are 800mils, 1200mils, 2700mils from the power pin
• C=1uF• ESL=0.5nH• ESR=1Ω
October 2007 Dr. Bruce Archambeault 83
Effect of Multiple Capacitors While Keeping Total Capacitance Constant
(power-ground pins at IC center)
12”
10”
Port1 (8,7)(Ls 50nH)
Port2 (4,5)(power pin)
εr =4.5
Decap
Ground pin1 inch
The decap locations are 800mils, 1200mils, 2700mils from the power pin
• C=0.5uF• ESL=0.5nH• ESR=1Ω
October 2007 Dr. Bruce Archambeault 84
Effect of Multiple Capacitors While Keeping Total Capacitance Constant
(power-ground pins at IC center)
12”
10”
Port1 (8,7)(Ls 50nH)
Port2 (4,5)(power pin) εr =4.5
Decap
Ground pin1 inch
The decap locations are 800mils, 1200mils, 2700mils from the power pin
• C=0.25uF • ESL=0.5nH• ESR=1Ω
October 2007 Dr. Bruce Archambeault 85
Constant Capacitance 800 mil Distance
October 2007 Dr. Bruce Archambeault 86
Constant Capacitance 800 mil Distance
October 2007 Dr. Bruce Archambeault 87
Constant Capacitance 1200 mil Distance
October 2007 Dr. Bruce Archambeault 88
Constant Capacitance 1200 mil Distance
October 2007 Dr. Bruce Archambeault 89
Constant Capacitance 2700 mil Distance
October 2007 Dr. Bruce Archambeault 90
Constant Capacitance 2700 mil Distance
October 2007 Dr. Bruce Archambeault 91
Example #1 Low Cap Connection Inductance
IC
GND
PWR
Cap
PCB
October 2007 Dr. Bruce Archambeault 92
Example #2 High Cap Connection Inductance
IC
GND
PWR
Cap
PCB
October 2007 Dr. Bruce Archambeault 93
Example #1 Hi Cap Connection Inductance
IC
GND
PWR
Cap
PCB
October 2007 Dr. Bruce Archambeault 94
Example #1 Lower Cap Connection Inductance
IC
GND
PWR
Cap
PCB
October 2007 Dr. Bruce Archambeault 95
Do’s Don’ts
Mutual Inductance Helps Reduce Path Inductance
J. L Knighten, B. Archambeault, J. Fan, et. al., “PDN Design Strategies: II. Ceramic SMT Decoupling Capacitors – Does Location Matter?,” IEEE EMC Society Newsletter, Issue No. 207, Winter 2006, pp. 56-67.
October 2007 Dr. Bruce Archambeault 96
Effect of Capacitor Value??
• Need enough charge to supply need• Depends on connection inductance
Charge = C*V
October 2007 Dr. Bruce Archambeault 97
Time Domain Noise Voltage Across Simulated IC Power/GND Pin (1 amp)Single Capacitor (with No L) with Various Capacitor Values
-0.4
-0.3
-0.2
-0.1
0
0.1
0.2
0.3
0.4
0.5
0.6
0 0.5 1 1.5 2 2.5 3 3.5 4
Time (ns)
Leve
l (vo
lts)
750ps Rise, 10 mil planes, (0.0 nH) 1uF @ 400mils
750ps Rise, 10 mil planes,0.01uF @ 400mils
750ps Rise, 10 mil planes, 100pF @ 400mils
October 2007 Dr. Bruce Archambeault 98
Time Domain Noise Voltage Across Simulated IC Power/GND Pin (1 amp)Single Capacitor (with 0.5 nH Connection L) with Various Capacitor Values
-0.4
-0.3
-0.2
-0.1
0
0.1
0.2
0.3
0.4
0.5
0.6
0 0.5 1 1.5 2 2.5 3 3.5 4
Time (ns)
Leve
l (vo
lts)
750ps Rise, 10 mil planes, (0.5nH) 1uF @ 400mils
750ps Rise, 10 mil planes, (0.5nH) 0.01 uF @ 400mils
750ps Rise, 10 mil planes, (0.5nH) 100 pF @ 400mils
October 2007 Dr. Bruce Archambeault 99
Time Domain Noise Voltage Across Simulated IC Power/GND Pin (1 amp)Single Capacitor (with 1 nH Connection L) with Various Capacitor Values
-0.4
-0.3
-0.2
-0.1
0
0.1
0.2
0.3
0.4
0.5
0.6
0 0.5 1 1.5 2 2.5 3 3.5 4
Time (ns)
Leve
l (vo
lts)
750ps Rise, 10 mil planes, (1nH) 1uF @ 400mils
750ps Rise, 10 mil planes, (1nH) 0.01uF @ 400mils
750ps Rise, 10 mil planes, (1nH) 1000pF @ 400mils
750ps Rise, 10 mil planes, (1nH) 100pF @ 400mils
October 2007 Dr. Bruce Archambeault 100
Noise Voltage is INDEPENDENT of Amount of Capacitance!
As long as there is ‘enough’ charge
Dist=400 mils
ESR=30mOhms
ESL=0.5nH
October 2007 Dr. Bruce Archambeault 101
Decoupling Summary (1)
• EMC Frequency Domain analysis– Steady-state conditions resonances– Transfer function across the board– Measurements and simulations agree well– Distance of capacitors from ASIC load does
not change steady-state impedance
October 2007 Dr. Bruce Archambeault 102
Decoupling Summary (2)
• Charge Delivery Time-Limited analysis– Using equivalent SPICE circuit from simulations– Current from capacitors change significantly as
capacitor moves further away from ASIC– Noise at ASIC pins increase significantly as capacitor
moves further away from ASIC– Steady-state frequency domain analysis not sufficient
for charge delivery design of decoupling capacitors
October 2007 Dr. Bruce Archambeault 103
Decoupling Summary (3)
• Recharge the planes– Location of Capacitor does matter!
• Effect more significant for thick dielectrics– Connection Inductance is important– Value of capacitance not important– More capacitors is better than
larger/fewer capacitors
October 2007 Dr. Bruce Archambeault 104
IEEE