research of a high-precision high-power-factor switching ......submitted july 2016; revised oct. 15,...
TRANSCRIPT
188
AMSE JOURNALS-2016-Series: Modelling A; Vol. 89; N°1; pp 188-204
Submitted July 2016; Revised Oct. 15, 2016, Accepted Dec. 10, 2016
Research of a High-Precision High-Power-Factor Switching Power
Supply
*Zhi Cui, **Xianpu Cui
* School of Communication and Electronic Engineering, Hunan City University
China, No. 518, East Yingbin Road, Yiyang, ([email protected])
** School of Communication and Electronic Engineering, Hunan City University
China, No. 518, East Yingbin Road, Yiyang, ([email protected])
Abstract
We design a novel type of switching power supply which is an integration of flyback type
and half-bridge resonant typology. Based on signal flow graph and division of functional modules
of the circuit, we elaborate on the design principle, functions of different modules and working
process of the switching power supply. By using three-terminal adjustable shunt regulator TL431,
LD7535 and L6599, the voltage control of the power supply and voltage stabilizing are realized
by regulating the pulse width and pulse frequency, respectively. The power factor is increased by
adopting active power factor correction. Experiment shows that the switching power supply has
good voltage stabilizing performance, with small ripple and high power factor as well as high
voltage regulation and load regulation.
Key words
Switching power supply, fly back, half-bridge resonant typology, high precision
1. Introduction
Switching power supply is a DC voltage-stabilizing power supply which uses the switching
regulator [1]. It regulates the output voltage by adjusting the switching frequency or duty cycle.
Because of its small size, light weight and high frequency, the switching power supply is applied
in nearly all electronic devices and plays an irreplaceable role in today’s electronic information
industry [2]. In the meantime, the requirement on the switching power supply is also rising in
other new fields. Addressing the defects of low precision and low power factor in ordinary
189
switching power supply, we design a novel type of switching power supply that is the
combination of flyback type and half-bridge resonant typology. By designing closed-loop
feedback control and employing active power factor correction, the precise control of the output
voltage and the improvement of power factor are realized.
Switching power supply consists of input circuit, power factor correction circuit, pulse
control circuit, power conversion circuit, output circuit, and feedback circuit. In our design, the
first module is the input circuit. The 220V AC current passes through the protection circuit, EMI
suppression filter and bridge rectifier, and the unstabilized DC voltage is obtained. This voltage is
subject to power factor correction in the second module, which maintains the same phase
between the input current and the input voltage. The third module is the power conversion circuit,
which uses the switching tube to convert DC voltage into a pulse waveform with certain
frequency and to transmit the energy to the output terminal. The fourth module is the output
circuit, where the square wave pulse voltage is rectified, filtered and converted into DC voltage.
The fifth module is the feedback control circuit, where the output voltage passes through the
voltage divider and the sampler and is compared against the reference voltage and amplified. The
feedback circuit incorporates the precision shunt regulator TL431 and optical coupler PC817C.
Upon receiving the output voltage feedback, the control chip will output the pulse width
modulation (PWM) signals, thus achieving high-precision voltage stabilizing.
2. Functional requirements and technical indicators
The purpose of this paper is to design a novel type of switching power supply which is an
integration of flyback type and half-bridge resonant typology.
2.1 Efficiency and power factor of the power supply
Within the given range of input voltage and temperature, the table below presents the target
range of output efficiency and power factor of the power supply. To calculate the overall
efficiency, the output power is first obtained based on the product of output current and output
voltage under the rated input voltage and output full load. Then the ratio of the output power to
the input active power on the power meter is calculated as the overall efficiency. The power
factor is the ratio of the input active power to the output apparent power [3].
190
2.2 Output voltage and current
Within the given range of input voltage and temperature, the table below presents the target
values of output current, voltage, ripple and noise. Ripple is a component synchronized with the
input frequency and switching frequency between the output terminals. Ripple is usually
expressed as the peak-to-peak value and should be below 0.5% of the output voltage. Noise is
another high-frequency component besides the ripple and should be about 1% of the output
voltage [4].
Tab. 1 Efficiency and power factor of power supply
Input voltage Output load Efficiency PF value
90VAC rating ≧84% ≧98%
264VAC rating ≧88% ≧93%
Tab. 2 Output voltage and current
V1 V2 V3 V4
Output Voltage +12V +24V +5V +5Vsb
Peak Current 2.5A 5A 3.5A 1A
Rated Current 2A 4A 3A 0.5A
Voltage
Regulation
Factor
±5% ±5% ±5% ±5%
Ripple 60mV 180mV 30mV 30mV
Ripple and
Noise 120mV 240mV 50mV 50mV
3. Detailed Process of Design
In this section, we will present the detailed process of design.
3.1 Input protection circuit
Input protection circuit consists of tube fuse, negative temperature coefficient (NTC)
thermistor and voltage dependent resistor. When the power supply has just started up, NTC
thermistor has low temperature and high resistance, offering instantaneous restraint to the
charging current [5]. As the heat dissipated by the current increases, the resistance of NTC
191
thermistor decreases rapidly. Thus NTC thermistor is started up and the power consumption is
reduced.
Voltage dependent resistor absorbs the voltage surges from the grid, which are generated
due to disturbances from the electrical equipments in the grid or natural lightning. Voltage surges
can take place within a very short time and reach very high values, causing the fuse and other
components in the power supply to burn out. Therefore, it is necessary to apply the voltage
dependent resistor across the two ends of the input voltage, so as to divide and absorb the voltage
and to protect the circuit.
1
3
CN1 AC INPUT
1 2
F1 T5A-L250V
T
NTC15D-11/13
CX1
0.47uFK/275V-X2
L
N
ZNR1 14D561K
Fig.1. Input protection circuit
3.2 EMI suppression filter
EMI. suppression filter is usually designed with a common mode inductor and a filter
capacitor. Common mode inductor is composed of two winding resistors with equal inductance in
a closed magnetic circuit [6]. The phase difference is 180 degrees due to the magnetic flux
generated by the frequency components of the power supply. Since the two resistors have equal
number of windings, they counteract each other and the inductance of the frequency components
of the power supply is zero. However, for the common mode noise, the effective permeability is
very high, leading to large attenuation.
14
23
LF1
*CY1
470pF/400VAC-X1Y1
CY2
470pF/400VAC-X1Y1
-4
AC
3
+1
AC
2 BD1
GBJ1006
R3
3.3M
R4
3.3M
R1
3.3M
R2
3.3M
14
23
LF2
*
CX2
0.22uFK/275V-X2
ZNR2
*14D561K
Fig.2. EMI suppression filter
192
3.3 Active power factor correction circuit
Power factor is the ratio of active power to apparent power [7]. In the electronic devices
containing AC/DC converter, the power supply for the DC/DC converter or DC/AC converter is
usually the DC voltage obtained by rectifying AC mains power and large-capacitance filtering.
The filter capacitor makes the output voltage smooth and the output current a spike pulse. If there
is no filter circuit after the rectifier circuit but only the resistive load, the input current will be the
sine wave having the same phase as the voltage of the power supply and a power factor of 1. The
basic principle of the active power factor correction circuit is to isolate the rectifier from the filter
capacitor, thus turning the capacitive load into resistive load in the rectifier circuit.
Power factor correction falls into two categories, active and inactive [8]. Active power factor
correction (APFC) circuit has an active power controller connected in series between the rectifier
and the output capacitor. As a result, the input current and input voltage of AC/DC converter will
be sine waves having the same frequency and the same phase. The input current is forced to go
with the input voltage, thus realizing unity power factor. APFC can improve the power factor and
overall efficiency of the switching power supply and prevent harmonic pollution of the grid. We
use analog integrated circuit L6562 for APFC.
193
HV1
C92
39 uF450V
D90
STTH10LCD06FP
HV C88
1uF50V
C93
39uF450V
HV1
R83
22K
C86
47pF1 KVR8910K
R840R( 470R)
NC6
FB4
MOS3
O
O
GND5
HV1
NC2
L81
SKY-DY201C
R8568K( 20K)
C810. 047uF200V
HV
G
DS
Q81
STP14NM50ZFP
C2CBB21-1uF/450V
INV1
COMP2
MULT3
CS4 ZCD 5
GND 6
GD7
VCC8
U81
L 6562D
C84
22pF50V
C83
0.01uF50V
R81
9K1( 10K)-F
VCC
R81M( 750K)
R101M(750K)
R91M( 750K)
C82
1uF50V
R8210K
C85
0.47uF50V
R97510K
R99510K
R98510K
R93
1R
R94
1R
R95
1R
R96
*1R
R9010R(4R7)
2 R92
0. 075R/2W
L82
FB
C90
100pF1KV
C91
39uF450V
1
R88
1R/1W
R86470R
Q82
PM3906
R9122R
R8747R
L 90
FB
Q 41
Fig.3. L6562 circuit
As shown in Fig. 3, the output voltage HV of the APFC passes through the sampling resistor
and then into the inverting input of the error amplifier through the pin INV. The reference voltage
of 2.5V is input to the non-inverting terminal. After amplification, it is input into the multiplier
M2. The AC voltage which has passed through the full-bridge rectifier is then sampled by the
voltage divider of the sampling resistor. It is input into multiplier M1 through the MULT pin. The
output voltage of the multiplier is proportional to the product of M1 and M2. The series
connected source resistor of power MOSFET is responsible for the sampling of the peak current
of drain voltage-increasing inductor L. It is input into the error amplifier via CS pin and
compared with the output voltage of the multiplier. When the voltage of the CS pin reaches the
threshold value, that is, when the current reaches the peak in L, the PWM comparator will stop
driving the gate of MOSFET.
194
3.4 Flyback typology
Flyback circuit refers to the following condition. When the switching tube is conducted,
driving the primary side of the pulse transformer, the secondary side of the transformer does not
supply power to the load [9]. This is the alternating conduction and disconnection of the primary
and secondary side. But due to leakage inductance of the transformer, the primary side will have
voltage spikes, causing the breakdown of the switching device. Therefore, it is necessary to
install the RCD clamp circuit. Single-terminal flyback driver circuit can satisfy the requirement
as a small-power high-frequency switching power supply. Furthermore, since the transformer in
the flyback typology switching power supply plays the dual roles of inductor and transformer,
only the filter capacitor needs to be selected, but not the filter inductor. The circuit structure is
simple. The typical isolated flyback driver circuit is shown in Fig. 4.
Trans
DC
GND
VOUT
LD7535
Fig.4. Isolated flyback driver circuit
LD7535, the pulse-width modulator, outputs the PWM signal to control the conduction and
disconnection of MOSFET. The working frequency is 50-130KHz and it is adjusted by grounding
a resistor through pin 3. The working frequency is 100K, and the corresponding switching
frequency is 65KHZ. When MOSFET is conducted, it stores energy in the primary coils of the
transformer. The diode connected to the secondary side of the transformer is in reverse biased
state and so the diode is disconnected. No current flows through the secondary circuit of the
transformer, and therefore no energy is supplied to the load. When MOSFET is disconnected, the
voltage polarity in the secondary coils of the transformer is reversed, thus conducting the diode
and charging the output capacitor. In the meantime, the current flows through the load.
3.5 Half-bridge resonant typology
Resonant power supply represents the new trend of switching power supply. The sine wave
is generated by the resonant circuit, and the switching tube is turned on and off during zero
195
crossing of the sine wave. Therefore, the MOS tube of the half-bridge circuit is alternately
conducted and disconnected. By regulating the switching frequency, the average output voltage
on the secondary side of the transformer can be changed. The half-bridge resonant typology
combined with APFC can achieve a power factor above 0.95, thus greatly inhibiting harmonic
pollution of the grid [10].
C701uF50V
R650R(1K)
C600.1uF50V
CSS1
DELAY2
CF3
RFMIN4
LVG11
STBY5
ISEN6
DIS8
LINE7
PFC_STOP9
NC13
OUT14
HVG15
VBOOT16
VCC12
GND10
U61
L6599A
R6712K
C68330pF(100pF)1KV
D66BAV99
HV
R71A0R(24K)
R7118K(24K)
G1
D2
S3
Q61
SVD7N60F
R7710K
G1
D2
S3
Q62
SVD7N60Fn
c
ZD61LBZX84C16LT1
nc
D63LMBD914LT1
VCC
C670.01uF50V
R63
2K4+330R(4K7)
HV
R6415K(24K)
C69
CBB21-0.022uF/630V
C63470pF50V
R681M
R701M
R691M
R66220R(820R)
C640.1uF50V
C65NC(100uF35V)
R614K7(12K)
C611uF50V
R62
750K(1M)
C620.47uF25V
R78A
NC(1K2)
Q64NC(S8550LT1)
R7847R(150R)
R75
10KR76A
NC(1K2)
Q63NC(S8550LT1)
R75ANC(20R)
R7647R(150R)
R77ANC(20R)
R720R(20R)
C71
Fig.5. L6599 circuit
L6599 is a double-ended controller specific for half-bridge resonant typology, outputting
signals with phase difference of 180° and 50% duty cycle. Unlike PWM controller, energy is
transmitted by adjusting the duty cycle. For the half-bridge resonant typology, the duty cycle is
fixed, so the energy transmission is controlled by the switching frequency. The output voltage is
controlled by the working frequency. As shown in Fig. 5, a resistor RF min is grounded via pin 4
for configuring the lowest oscillation frequency. Resistor RF max is grounded via pin 4. Photo-
coupled grounding is controlled by the feedback circuit and the oscillation frequency of the
controller is adjusted along with the output voltage. RF max is for configuring the highest
working frequency.
196
3.6 Output rectifier and filter circuit
The output voltage of the switching power supply needs to be rectified and filtered. Schottky
rectifier diode depends on the working of most charge carriers and can be conducted and
disconnected easily. It has a small positive voltage drop, which decreases with higher
temperature. Therefore, the loss arising from conduction is reduced. The following principles
should be adhered to when choosing the parameters of the output rectifier tube. The rated current
should be at least three times that of the maximum output current of the circuit. The working peak
reverse voltage should be higher than the minimum permissible voltage.
Output filter converts the AC square waves into DC current. As shown in Fig. 6, the rectified
waveform is directly input into the filter and smoothed into DC waveform by high-capacitance
filtering. L51 and C55 make up the post-filter that smooths the waveform and reduces ripple.
GND
D51STPS20LCD45CFP
C53
1000uF16V
L51 2uH
GND
C760.1uF50V
GND
C55
470uF16V
GND GND
+12V
C570.1uF50V
GND
C54
NC(1000uF16V)
GND
GND
D71MBRF20100CT
C73
1000(470)uF35V
L71 2uH
GND
R504K7
GND
C75
470uF35V
+24V
GND
C74
1000(470)uF35V
R7310K
R7410K
L52 FB
L72*FB
Fig.6. Output rectifier and filter circuit
3.7 Feedback voltage stabilizing circuit
Closed-loop feedback is used to stabilize the output voltage. Optical coupler is used for
input sampling, signal feedback and driving output. The feedback circuit is designed as shown in
Fig. 7. TL413 is a precision voltage stabilizer that stabilizes the voltage at pin 2 of the optical
coupler PC817C at 2.5V. When the output voltage of 24V increases, the voltage of pin 2 remains
constant, while the voltage of pin 1 increases. As a consequence, the light emitting device is
conducted and gives off light. The light receiver is also conducted and the voltage of pin 4
decreases. On the contrary, when the output voltage of 24V decreases, the light receiver is
disconnected and the voltage of pin 4 increases. The voltage level of pin 4 of PC817C is feedback
to the control chip. By regulating the duty cycle, the voltage is stabilized.
R54 and R56 are the output sampling resistors. They divide the output voltage by controlling
the shunt from the cathode to the anode via the REF terminal of TL431. This current directly
197
drives the light emission of the optical coupler. When the output voltage increases, Vref increases
as well, leading to increased current flowing through TL431. As a result, the light emitted by the
optical coupler becomes stronger and the feedback voltage at the light sensing terminal increases
as well. The PWM control chip, upon receiving this feedback voltage, will change the switching
time of MOSFET and the output voltage will drop.
R513K9
A1
K2
C4
E3
U62
PC817B
R534K7
C510.01uF50V
R566K8-F
GND GND
R1
A2
K3
U63
TL431
R521K
+12V +24V
R5420K-F
R576K8-F
GND
R5582K-F
Fig.7. Feedback circuit
4. The Main Hardware Circuit
The circuit diagram consists of three parts, namely, input circuit and APFC module,
flyback typology, half-bridge resonant typology and PCB design. For each part, the circuit
diagrams are shown in Fig. 8, Fig. 9, Fig. 10, and Fig. 11, respectively.
198
HV1
C92
39uF450V
D90STTH10LCD06FP
HV C88
1uF50V
C93
39uF450V
HV1
R8322K
C8647pF1KV
R8910K
R840R(470R)
NC6
FB4
MOS3
O
O
GND5
HV1
NC2
L81SKY-DY201C
R8568K(20K)
C810.047uF200V
HV
G
DS
Q81
STP14NM50ZFP
C1CBB21-1uF/450V
C2CBB21-1uF/450V
L1
150uH
INV1
COMP2
MULT3
CS4
ZCD5
GND6
GD7
VCC8
U81L6562D
C84
22pF50V
C830.01uF50V
R81
9K1(10K)-F
VCC
R81M(750K)
R101M(750K)
R91M(750K)
C821uF50V
R8210K
C850.47uF50V
R97510K
R99510K
R98510K
R931R
R941R
R951R
R96*1R
R9010R(4R7)
2 R920.075R/2W
L82
FB
C90100pF1KV
C91
39uF450V
1 R881R/1W
R86470R
Q82
PM3906
R9122R
R8747R
L90FB
1
3
CN1
AC INPUT
14
23
LF1
*
1 2
F1T5A-L250V
T
NTC15D-11/13
CY1470pF/400VAC-X1Y1
CY2470pF/400VAC-X1Y1
-4
AC
3
+1
AC
2
BD1
GBJ1006CX1
0.47uFK/275V-X2
R3
3.3M
R4
3.3M
Text
L
N
R1
3.3M
R2
3.3M
14
23
LF2
*
ZNR114D561K
CX20.22uFK/275V-X2
ZNR2*14D561K
GN
D4
GN
D1
GN
D2
GN
D3
HS2KYX-TXT-022A
HV
VCC
HV1HV1
HV
VCC
Fig.8. Input circuit and APFC module
HVGND
6
FB7
HV2
MOS4
5V8
NC9
O
O
O
GND10
T1SKY-BCK-TD2215
GND1
COMP2
RF3
CS4
VDD5
GATE6
U1
LD7535M
1
R18100K/1W
C18
4.7nF400V
D14
HER207
R2610K
R24470R
nc D11
LMBD914LT1
C16
0.1(0.01)uF50V
R21100K
R23
1K
R274R7
Q3S8550LT1
Q2PM3904D
R2520R
R22150R
C1310uF50V
nc
ZD11LBZX84C16LT1
C15100pF50V
R141K(3K)
D13FR107
R11510K
R13510K
R12510K
C12
100(47)uF50V
L11FB
R284R7
R294R7
R303R3
R152R2
Q4
*PM3904D
C100.1uF50V
G1
D2
S3
Q1
SVD4N65F
VDD
VDD
VDD1
nc
ZD15*LBZX84C16LT1
nc
D10LMBD914LT1
C1122uF50V
Q5*PM3904D
C17
*1uF50V
R16*120K
C140.1uF50V
R17*39K
C9
*22uF16V
VDD1
R40*750K
R42*750K
R41*750K
C19
100pF1KV
C43
1000uF10V
D41
STPS20LCD45CFP
R4420R
C411nF50V
C48
470uF10V
R4320R
C470.1uF50V
+12V
C46
0.1uF50V
C450.22uF50V
nc
D42
LMBD914LT1
R45100K
G
D S
Q41
AOD452A
C42
1000uF10V
L412uH
GND
C44
470uF10V
+5VSB
GNDGND
+5V+5V1
GNDGND
GND
D41
D41
GND GND
A1
K2
C4
E3
U2
PC817B
R3310K
C310.47uF50V
R344.7K-F
R1
A2
K3
U3
TL431
R321K
R31220R
R0*0R
+5V1
+5VSB
R374.99K-F
C202.2nF400VAC
HV GND
1R20*4M/1W
GN
D4
GN
D1
GN
D2
GN
D3
HS1KYX-TXT-023A
+5VSB
HV
GND1
2
3
4
5
6
7
8
9
10
11
12
13
CN3
TJC3-13A-W
PSON
GND
+12V
+12V
+5VSB
GND
GND
GND
+5V
+5V
+5V
+5V
+12V
PSON
VDD1
HV1HV1
HV
+12V
+5VSB
VDD1
Fig.9. Flyback typology
199
C701uF50V
R650R(1K)
C60
0.1uF50VCSS
1
DELAY2
CF3
RFMIN4
LVG11
STBY5
ISEN6
DIS8
LINE7
PFC_STOP9
NC13
OUT14
HVG15
VBOOT16
VCC12
GND10
U61
L6599A
R6712K
C68330pF(100pF)1KV
D66BAV99
HV
R71A0R(24K)
L61FB
R7118K(24K)
G1
D2
S3
Q61
SVD7N60F
R7710K
G1
D2
S3
Q62
SVD7N60F
nc
ZD61LBZX84C16LT1
nc
D63LMBD914LT1
VCC
C670.01uF50V
R63
2K4+330R(4K7)
HV
R6415K(24K)
C69
CBB21-0.022uF/630V
C63470pF50V
R681M
R701M
R691M
R66220R(820R)
C640.1uF50V
C65NC(100uF35V)
R61
4K7(12K)
C611uF50V
R62750K(1M)
C620.47uF25V
R60
NC(100K)
R78A
NC(1K2)
Q64NC(S8550LT1)
R7847R(150R)
R75
10KR76A
NC(1K2)
Q63NC(S8550LT1)
R75ANC(20R)
R7647R(150R)
R77ANC(20R)
R720R(20R)
C71
NC
(10
0p
F1
KV
)
C661nF50V(NC)
MOS6
CAP7
GND3
GND5
GND14
12V8
GND4
12V9
GND13
O
OO
24V11
GND2
O
24V10
GND12
O
T61SKY-BCK-TGW4210
GND
D51STPS20LCD45CFP
GND
D71MBRF20100CT
GND
R513K9
A1
K2
C4
E3
U62
PC817B
R534K7
C510.01uF50V
R566K8-F
GND GND
R1
A2
K3
U63
TL431
R521K
+12V +24V
R5420K-F
R576K8-F
GND
R5582K-F
GND GND GND
GND GND
+12V
GND GND
GND GND GND
+24V
GND
C53
1000uF16V
L512uH
C760.1uF50V
C55
470uF16V
C570.1uF50V
C54
NC(1000uF16V)
C73
1000(470)uF35V
L712uH
R504K7
C75
470uF35V
C74
1000(470)uF35V
R7310K
R7410K
L52 FB
L72*FB
D51
D71
D71
D51
GN
D4
GN
D1
GN
D2
GN
D3
HS3KYX-TXT-023A
GNDGND GNDGND
1
2
3
4
CN4TJC3-4A-W
+24V
+24V
GND
GND
HV
+12V
+24V
VCC
GND
GND
GND
GND
1
2
3
4
5
6
7
8
CN5TJC3-8A-W
+24V
HV
+12V
+24V
VCC
Fig.10. Half-bridge resonant typology
Fig.11. PCB design
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5. Experiment and discussion
The performance test of switching power supply is important for performance evaluation.
The test items include overall efficiency, power factor, cross loading, ripple and noise, output
voltage overshoot and temperature rise. Here the equipment tested is composed of 3KW AC auto
transformer, CHROMA 650 electronic load, TDS3032B oscilloscope and P6021 current probe.
5.1 Overall efficiency and power factor
Overall efficiency and power factor are tested to see if they satisfy the requirement. Under
AC220V/50HZ, the overall efficiency should be no less than 85% and the power factor no less
than 0.92 when the overall power of the power supply is smaller than 1500W.
Tab. 3 Test result of overall efficiency and power factor of the power supply
Full Load(%) 80% Load(%) Half Load(%)
PF Efficiency PF Efficiency PF Efficiency
90V 99.7 86.01 99.7 86.90 99.6 86.87
120V 99.5 88.24 99.6 88.45 99.3 88.10
160V 99.5 89.22 99.2 89.40 98.3 88.68
220V 98.3 89.98 97.7 89.99 96.8 89.03
264V 96.7 90.16 95.2 90.21 94.3 89.03
As shown in Tab. 3, the minimum efficiency is 86.01% and the maximum is 90.21% under
different loads; the minimum power factor is 94.3% and the maximum power factor is 99.7%.
The performance is excellent and satisfies the requirement.
5.2 Cross loading test
Cross loading test is to evaluate the voltage regulation capacity under unbalanced load. It is
checked whether the output voltage varies with the load and whether the variation range of the
output voltage exceeds the specified value.
As shown in Tab. 4, when output voltage is 5V and 12V (heavy load) and the output voltage
is 24V (light load), the actual output voltage is 24.64V under the load of 24V. Thus, under
unbalanced load with multi-route output, the output voltage fluctuates greatly. We use the TL431
precision shunt regulator for feedback regulation and achieve satisfactory effect.
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5.3 Ripple and Noise
Ripple and noise are tested as well. The high-frequency and low-frequency ripple and noise
are displayed on the oscilloscope. For this test, a 47uF capacity together with a 0.1uF capacitor is
connected to the voltage probe of the oscilloscope. The test is performed at broadband 20MHz
AC mode. Under input voltage of 240V and full load condition, the ripple and noise of the three
output routes are shown as follow.
Tab. 4 Result of cross loading test
5V 12V 24V 5V 12V 24V
0.1A 0.3A 0.2A 5.16V 11.97V 24.22V
0.1A 0.3A 4.0A 5.16V 12.04V 23.91V
0.1A 2.0A 0.2A 5.15V 11.88V 24.63V
3.0A 0.3A 0.2A 5.12V 11.97V 24.24V
0.1A 2.0A 4.0A 5.15V 11.95V 24.30V
3.0A 0.3A 4.0A 5.12V 12.04V 23.93V
3.0A 2.0A 0.2A 5.11V 11.88V 24.64V
3.0A 2.0A 4.0A 5.11V 11.95V 24.32V
Tab. 5 Test result of ripple and noise
Load Ripple Ripple and Noise
5V 3A 09.6mv 15.6mv
12V 2A 37.8mv 52.8mv
24V 4A 117.0mv 181.0mv
Fig. 12 5 V ripple Fig. 13 12V ripple Fig. 14 24V ripple
Ripple is a component synchronized with the input frequency and switching frequency
between the output terminals. Expressed as the peak-to-peak value, ripple is usually below 0.5%
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of the output voltage. Noise is a high-frequency component between the output terminals and its
value is about 1% of the output voltage. Ripple noise is the synthesis of the two and generally
below 2% of the output voltage. As shown in Tab. 5, the ripple and noise in all three output
routes satisfy the requirement.
5.4 Output voltage overshoot and time-to-climb
Output voltage overshoot and time-to-climb are the peak values causing the changes of DC
voltage when the power supply is turned on or off. When the power supply is turned on, the
voltage overshoot and time-to-climb are recorded with the oscilloscope. Under the input voltage
of 220V and full load conditions, the output voltage overshoot and time-to-climb are measured as
follows.
Tab. 6 Output voltage overshoot and time-to-climb
Output Voltage Load Current Overshoot Rise Time
+5V MAX 0.000% 01.6ms
+12V MAX 3.840% 06.8ms
+24V MAX 2.789% 05.6ms
Fig. 15 5V overshoot Fig. 16 12V overshoot Fig. 17 24V overshoot
According to relevant standards, the overshoot of the power supply should not exceed ±10%
of the output voltage. In Tab. 6, the maximum overshoot is 3.84%, which satisfies the
requirement.
Conclusion
Switching power supply is now considered a substitute for linear power supply due to its
various advantages. We design a novel type of switching power supply with three outputs (5V,
12V, 24V) by combining flyback circuit and half-bridge resonant typology and using TL431
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circuit and PC817 optical coupler. The experiment shows that this switching power supply has
good voltage stabilizing performance, with small ripple, high power factor, high voltage
regulation and high load regulation. Compared with ordinary switching power supply, the
proposed power supply has higher precision of output voltage, higher power factor, smaller
ripple, lower load regulation and voltage regulation. Moreover, the power is larger and the load-
carrying capacity is improved.
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